A system for phase control of a Phased Locked Loop, PLL, is disclosed. The system includes the PLL. The PLL includes an oscillator configured to generate an output signal; a frequency divider configured to generate a feedback signal by dividing the output signal from the oscillator; a first phase detector arrangement configured to output a first control signal to control the oscillator in response to a detection of a phase deviation between a reference signal and the feedback signal. A second phase detector is configured to receive the feedback signal from the frequency divider and the reference signal, and generate an output signal. A phase calibration circuit is configured to receive the output signal from the second phase detector and generate a second control signal to adjust a phase of the output signal of the oscillator.

A fast chirp Phase Locked Loop (70) with a boosted return time includes a Voltage Controlled Oscillator, VCO, (12) generating a Frequency Modulated Continuous Waveform, FMCW, (14). The VCO responds to a filtered output voltage (74) of a filter (72) connected to a charge pump (28). A digital controller (82) modifies the FMCW to generate a chirp phase (304) and a return phase (300). The chirp phase includes a first linear change of the FMCW from a start frequency (202) to a stop frequency (204). The return phase includes a second linear change of the FMCW from the stop frequency to the start frequency. A boost circuit (86) connects to the digital controller and the filter. The boost circuit supplies a boost current (98) during the return phase. The boost current is proportional to a return slope of the return phase and inversely proportional to a VCO gain of the VCO.

A fast chirp Phase Locked Loop (70) with a phase preset includes a Voltage Controlled Oscillator, VCO, (12) generating a Frequency Modulated Continuous Waveform, FMCW, (14). The VCO responds to a filtered output voltage (74) of a filter (72) connected to a charge pump (28). A digital controller (82) modifies the FMCW to generate a chirp phase (304) and a return phase (300). The chirp phase includes a first linear change of the FMCW from a start frequency (202) to a stop frequency (204). The return phase includes a second linear change of the FMCW from the stop frequency to the start frequency. A phase preset circuit (86) connects to the digital controller and the filter. The phase preset circuit supplies a phase preset current (98) during a start frequency time (302) preceding the chirp phase. The phase preset current is proportional to a VCO gain of the VCO and inversely proportional to a chirp current during the chirp phase.

A method of a control circuit of a communication device comprises: receiving a data signal to generate a phase data signal to a digital phase-locked loop (DPLL); using the DPLL to receive the phase data signal, to dynamically lock a particular clock, and to generate a phase modulation signal based on the phase data signal; and determining or adjusting an equivalent capacitance of an inter-stage circuit which is coupled between the DPLL and a power amplifier and configured for processing the phase modulation signal and generating a processed phase modulation signal to the power amplifier.

A wireless communication device includes a receiver circuit, a phase shift control circuit, and a digital phase-locked loop (DPLL) circuit. The receiver circuit includes a down-converter circuit that is used to apply down-conversion to an input signal according to a local oscillator (LO) signal. The phase shift control circuit is used to generate a phase shift signal. The DPLL circuit is used to generate the LO signal locked to an initial frequency under a frequency-lock state. In response to the phase shift signal, the DPLL circuit is further used to make the LO signal have a different frequency without leaving the frequency-lock state.

A frequency generator is disclosed. The frequency generator is for generating an oscillator clock according to a reference clock, and the frequency generator is used in a frequency hopping system that switches a carrier frequency among a plurality of channels, and the carrier frequency further carries a modulation frequency for data transmission. The frequency generator includes: a frequency hopping and modulation control unit, arranged for generating a current channel according to a channel hopping sequence and a frequency command word (FCW) based on the reference clock, a digital-controlled oscillator (DCO), arranged for to generating the oscillator clock according to an oscillator tuning word (OTW) obtained according to the estimated DCO normalization value. An associated method is also disclosed.

Various methods provide for trimming the gain in a dual-port phase-locked loop (PLL) of a radio transceiver. Use is made of the radio's demodulator to perform modulation accuracy measurements, thereby reducing the cost and complexity of external test equipment.

Interfaces between clock domains of an integrated circuit (IC) depend on synchronization of phase-locked loops (PLLs) that generate clocks in the different domains and on how each PLL responds to jitter in a shared reference clock. The well-controlled same bandwidth (and loop dynamic) for those PLLs renders the same and, therefore, ignorable reference jitter contribution. As a key component that determines a digital PLL bandwidth, digitally controlled oscillator (DCO) may have its gain vary with process, temperature, and supply IR drop from chip to chip or even module to module. A calibration circuit provides a gain correction factor to achieve a nominal gain in DCO as well as a desired/target PLL loop bandwidth. In some examples, the calibration circuit in each PLL determines a gain correction factor that causes the PLLs to have a common jitter response and stores the gain correction factors in the calibration circuits.

Various methods provide for trimming the gain in a dual-port phase-locked loop (PLL) of a radio transceiver. Use is made of the radio's demodulator to perform modulation accuracy measurements, thereby reducing the cost and complexity of external test equipment.

The method for calibrating the frequency synthesizer using two-point FSK modulation consists, in a first phase, in supplying an excitation signal generated by a calibration unit to a sigma-delta modulator by deactivating a digital-to-analog converter and transmitting the output signal from a loop filter of the synthesizer to the calibration unit, which digitally converts the incoming signal and offsets the phase shift between the excitation signal and the loop filter output signal in the calibration unit. In a second phase, the excitation signal is supplied to the sigma-delta modulator and to the activated digital-to-analog converter, and the digital-to-analog converter gain is calibrated by checking, in the calibration unit, the polarity of the loop filter output signal with respect to the excitation signal, and using a dichotomy algorithm.