A frequency-modulated continuous-wave radar system includes a waveform generator, a delta-sigma modulation circuit, a voltage controlled oscillator, a frequency divider circuit, a control circuit, an injection locked oscillator, a power amplifier circuit, a first power detection circuit, a second power detection circuit, a third power detection circuit, and a calibration engine circuit. The waveform generator, the delta-sigma modulation circuit, the voltage controlled oscillator, the frequency divider circuit, and the control circuit form a phase locked loop. The calibration engine circuit is coupled to the delta-sigma modulation circuit, the voltage controlled oscillator, the injection locked oscillator, the power amplifier circuit, the first power detection circuit, the second power detection circuit, and the third power detection circuit for adjusting frequency gains of the voltage controlled oscillator, the injection locked oscillator, and the power amplifier circuit to approach wideband flatness frequency responses.

An oscillating circuit has an injection-locked oscillator (ILO) and a calibration circuit. The ILO has a Gm cell and an LC tank. A first node of the Gm cell receives a first injection signal, and a second node of the Gm cell receives a second injection signal. The first injection signal and the second injection signal are differential signals. The Gm cell provides a negative resistance between a first output end and a second output end of the Gm cell. When the calibration circuit tunes a resonant frequency of the LC tank of the ILO, the magnitude of the negative resistance is reduced to control the ILO to stop self-oscillating. After finishing tuning the resonant frequency of the LC tank, the calibration circuit controls the ILO to start self-oscillating by increasing the magnitude of the negative resistance.

A method for enhancing linearity of the receiver front-end system includes receiving a radio frequency signal by an antenna, converting the radio frequency signal to first differential signals by a transformer module, adjusting frequencies of the first differential signals to generate second differential signals by a mixer module, detecting a common signal in order to reduce a common error of the second differential signals, and generating third differential signals according to a reference signal after the common error is reduced from the second differential signals. The first differential signals, the second differential signals, and the third differential signals are unbalanced.

A low voltage inverter-based amplifier includes a first inverter-based amplification module, a second inverter-based amplification module, an inverter-based feedforward module, and an inverter-based common mode detector. The first inverter-based amplification module receives an input signal. The second inverter-based amplification module receives the input signal through the inverter-based feedforward module, and receives a first output signal from the first inverter-based amplification module. The inverter-based common mode detector receives an amplified signal from the second inverter-based amplification module, and outputs a feedback signal to the second inverter-based amplification module. Since the first and the second inverter-based amplification modules are both inverter-based, the supply voltage of the low voltage inverter-based amplifier is provided to supply one PMOS and one NMOS for normal operation. Therefore, a number of cascade MOSs of the low voltage inverter-based amplifier is two, and the low voltage inverter-based amplifier can be normally operated under the low supply voltage.

A divider-less phase locked loop (PLL) includes a phase frequency detector (PFD), a charge pump (CP), a voltage controlled oscillator (VCO), a delay unit, and a clock gating unit. The PFD is electrically connected to the VCO through the CP, and the CP outputs a voltage control signal to the VCO. The VCO generates an output signal. The delay unit receives and delays a reference signal to generate a delay signal. The clock gating unit samples the output signal according to the delay signal. Since the clock gating unit samples the output signal according to the delay signal, the divider-less PLL does not need to include a divider to divide a frequency of the output signal. Therefore, power consumption of the divider-less PLL can be reduced.

A divider-less phase locked loop (PLL) includes a phase frequency detector (PFD), a charge pump (CP), a voltage controlled oscillator (VCO), a delay unit, and a clock gating unit. The PFD is electrically connected to the VCO through the CP, and the CP outputs a voltage control signal to the VCO. The VCO generates an output signal. The delay unit receives and delays a reference signal to generate a delay signal. The clock gating unit samples the output signal according to the delay signal. Since the clock gating unit samples the output signal according to the delay signal, the divider-less PLL does not need to include a divider to divide a frequency of the output signal. Therefore, power consumption of the divider-less PLL can be reduced.

There is provided a chopper stabilized amplifier with an input bias current reduced. The chopper stabilized amplifier includes a main amplifier and a correction circuit. The correction circuit includes a second gm amplifier of a full differential type. A first selector and the second gm amplifier are coupled to each other without DC blocking capacitors. The differential input state of the second gm amplifier is configured with a depletion-type transistor.

A communication circuit may include a first pair of digital-to-analog converters (DACs) coupled to an input of a first mixer and configured to generate first baseband signals. The communication circuit may further include a second pair of DACs coupled to an input of a second mixer and configured to generate second baseband signals. The second baseband signals may be shifted in phase relative to the first baseband signals.

An amplifier includes an input stage, a folded cascode stage, and a class AB output stage. The folded cascode stage is coupled to the input stage. The class AB output stage is coupled to the folded cascode stage. The class AB output stage includes a high-side output transistor, a low-side output transistor, and a high-side feedback circuit that is coupled to the high-side output transistor. The high-side feedback circuit includes a high-side sense transistor and a high-side feedback transistor. The high-side sense transistor includes a control terminal that is coupled to a control terminal of the high-side output transistor. The high-side feedback transistor is coupled to an output of the high-side sense transistor and to the folded cascode stage. A first output of the folded cascode stage is coupled to the control terminal of the high-side sense transistor and to the control terminal of the high-side output transistor.

A two-stage operational amplifier is provided to comprise a bias voltage generator, a first stage operational amplifier and a second stage operational amplifier, wherein the first stage operational amplifier comprises a folded cascode amplifier circuit and a cross coupling load, the cross coupling load is coupled to a load differential pair in the folded cascode amplifier circuit, the cross coupling load comprises two transistors, the two transistors in the cross coupling load and two transistors in the load differential pair constitute two current mirror structures, which are cross coupled. In the solution, the cross coupling load is added to the load differential pair in the folded cascode amplifier circuit, to increase gain of the two-stage operational amplifier by using positive feedback and negative conductance gain enhancement technology; while parameters of MOSFETs in the folded cascode amplifier circuit are properly set to reduce noise of the two-stage operational amplifier.