SYSTEM FOR TRANSMITTING ELECTRICAL ENERGY
20220199319 · 2022-06-23
Inventors
- Andrey Borisovich TARASOV (Moscow, RU)
- Oleg Vladimirovich TRUBNIKOV (Moscow, RU)
- Konstantin Victorovich SAPRYKIN (Moscow, RU)
Cpc classification
H01F29/06
ELECTRICITY
H01F29/02
ELECTRICITY
International classification
Abstract
Provided is a system for transmitting electrical energy comprising: transmitting and receiving quarter-wave resonant transformers, the quarter-wave winding of each of which is provided with contact terminals; a source of electrical energy connected to a coupling coil configured to establish a magneto-inductive link with the quarter-wave winding of the transmitting transformer with providing the possibility of exciting resonant oscillations in the quarter-wave winding of the transmitting transformer; a receiver of electrical energy connected to a coupling coil configured to establish a magneto-inductive link with the quarter-wave winding of the receiving transformer with providing the possibility of receiving electrical energy from the quarter-wave winding of the receiving transformer; an electrical energy transmission line connecting inter se the low-potential portions of the quarter-wave windings of said receiving and transmitting transformers so as to transmit electrical energy therebetween with providing the possibility of exciting resonant oscillations in the quarter-wave winding of the receiving transformer, wherein a sliding contact is connected to the high-potential terminal of each of said quarter-wave transformers, the sliding contact being configured to move along the quarter-wave winding of the quarter-wave transformer with providing the possibility of connecting to one of the contact terminals thereof.
Claims
1. A system for transmitting electrical energy comprising: transmitting and receiving quarter-wave resonant transformers, the quarter-wave winding of each of which is provided with contact terminals, a source of electrical energy connected to a coupling coil configured to establish a magneto-inductive link with the quarter-wave winding of the transmitting transformer with providing the possibility of exciting resonant oscillations in the quarter-wave winding of the transmitting transformer, a receiver of electrical energy connected to a coupling coil configured to establish a magneto-inductive link with the quarter-wave winding of the receiving transformer with providing the possibility of receiving electrical energy from the quarter-wave winding of the receiving transformer, an electrical energy transmission line connecting inter se the low-potential portions of the quarter-wave windings of said receiving and transmitting transformers so as to transmit electrical energy therebetween with providing the possibility of exciting resonant oscillations in the quarter-wave winding of the receiving transformer, wherein a sliding contact is connected to the high-potential terminal of each of said quarter-wave transformers, the sliding contact being configured to move along the quarter-wave winding of the quarter-wave transformer with providing the possibility of connecting to one of the contact terminals thereof.
2. The system according to claim 1, wherein the source of electrical energy is an alternating current source, and the receiver of electrical energy is a direct current receiver, wherein said receiver is connected to the coupling coil on the side of the receiving quarter-wave transformer by means of an alternating current to direct current converter.
3. The system according to claim 1, wherein the source of electrical energy is a direct current source, and the receiver of electrical energy is an alternating current receiver, said receiver being connected to the coupling coil on the side of the transmitting quarter-wave transformer by means of a direct current to alternating current converter.
4. The system according to claim 1, wherein the source of electrical energy is a direct current source, and the receiver of electrical energy is a direct current receiver, said source being connected to the coupling coil on the side of the transmitting quarter-wave transformer by means of an alternating current to direct current converter, and said receiver being connected to the coupling coil on the side of the receiving quarter-wave transformer by means of an alternating current to direct current converter.
5. The system according to claim 1, wherein the coupling coil on the side of the transmitting quarter-wave transformer has taps for connecting to an electrical energy source and is provided with a slider configured to move along the turns of said coupling coil with providing the possibility of connecting to one of said taps.
6. The system according to claim 1, wherein the coupling coil on the side of the receiving quarter-wave transformer has taps for connecting to an electrical energy receiver and is provided with a slider configured to move along the turns of said coupling coil with providing the possibility of connecting to one of said taps.
7. The system according to claim 1, wherein a further sliding contact configured to move along the turns of the low-potential portion of the quarter-wave winding of the transformer is connected to the low-potential terminal in each of the transmitting and receiving quarter-wave transformers by means of a grounded capacitor.
8. The system according to claim 1, wherein, to connect the high-potential terminal of each of said transmitting and receiving quarter-wave transformers to the corresponding one of the sliding contacts, a corresponding capacitor of predetermined capacitance is used.
9. The system according to claim 1, wherein, to connect the high-potential terminal of each of said transmitting and receiving quarter-wave transformers to the corresponding one of the sliding contacts, a corresponding capacitor of variable capacitance is used.
10. The system according to claim 1, wherein the high-potential terminal in each of said transmitting and receiving quarter-wave transformers is further connected to a solitary capacitor.
11. The system according to claims 1, wherein each of said transmitting and receiving transformers is a quarter-wave resonant Tesla transformer.
Description
BRIEF DESCRIPTION OF DRAWINGS
[0030] The attached drawings, which are provided for a better understanding of the essence of the present utility model, are an integral part hereof and are included herein to illustrate the below embodiments of the present utility model. The attached drawings, in combination with the description below, are intended to explain the essence of the present utility model. In the drawings:
[0031]
[0032]
[0033]
[0034]
[0035]
[0036]
[0037]
IMPLEMENTATION
[0038]
[0039] The system 100 comprises two resonant circuits, one of which is defined by a quarter-wave resonant transformer 1, and the other resonant circuit is defined by a quarter-wave resonant transformer 2, wherein the quarter-wave resonant transformers are electrically connected to each other by means of a single-wire electrical energy transmission line 3. It should be noted that the quarter-wave resonant transformer 1 may be configured as, for example, a quarter-wave resonant Tesla transformer and may function, in the system 100, as a transmitting transformer; the quarter-wave resonant transformer 2 may be configured as, for example, a quarter-wave resonant Tesla transformer and may function, in the system 100, as a receiving transformer. In a preferred embodiment of the present technical solution, the system 100 may use generally identical receiving and transmitting quarter-wave resonant Tesla transformers 1, 2 having generally identical design peculiarities of the winding and generally identical technical parameters.
[0040] In one of the embodiments of the present technical solution, the quarter-wave resonant transformers 1, 2 may each be configured as a quarter-wave resonant Tesla transformer, wherein the quarter-wave resonant Tesla transformer 1 may function, in the system 100, as a receiving transformer and have the design peculiarities and operating peculiarities described below in relation to the receiving resonant Tesla transformer, and the quarter-wave resonant Tesla transformer 2 function, in the system 100, as a transmitting transformer and have the design peculiarities and operating peculiarities described below in relation to the transmitting resonant Tesla transformer.
[0041] In another embodiment of the present invention, the quarter-wave resonant transformers 1, 2 may each be configured as a modified transformer, which is a set of concentrated coils, or windings that are distributed along the length or height.
[0042] Those skilled in the art will appreciate that the system 100 may consist of any number of resonant transformers that operate in a mode that will be equivalent to two quarter-wave resonant transformers. It is understood herein that the quarter-wave resonant transformer 1 may be made of any number of transformers, and the quarter-wave resonant transformer 2 may be made of any number of transformers.
[0043] As shown in
[0044] Those skilled in the art will appreciate that resonant transformers 1 and 2 are resonant circuits with distributed parameters and do not necessarily have to be configured as transformers, but may be configured as a single coil with distributed parameters or made from a set of two or more coils with concentrated parameters that are distributed in space.
[0045] Furthermore, as shown in
[0046] It should be noted that the tunable coupling coil 5 may be tuned using a sliding contact or slider 10 configured to move along the turns of the coupling coil 5 with providing the possibility of connecting to one of the taps 5.1, which allows to adjust or tune the actual parameters of the coupling coil 5 in the operating or design mode thereof. Similarly, the tunable coupling coil 6 may be tuned using a sliding contact or slider 11 configured to move along the turns of the coupling coil 6 with providing the possibility of connecting to one of the taps 6.1, which allows to adjust or tune the actual parameters of the coupling coil 6 in the operating mode thereof. In particular, moving the slider 10 with the provision of the connection thereof to one of the taps 5.1 provides the possibility to modify or tune the inductance (self-induction coefficient) of the coupling coil 5, which, inter alia, depends on the number of turns of the coil and which is essentially the main electrical parameter of the coupling coil 5, characterizing the amount of electrical energy that the coupling coil 5 can store when an electric current flows therethrough (the greater the inductance of the coupling coil 5, the more electrical energy it stores in the magnetic field thereof), and moving the slider 11 with the provision of the connection thereof to one of the taps 6.1 in the same fashion provides the possibility to modify or tune the inductance (self-induction coefficient) of the coupling coil 5.
[0047] It should further be noted that the coupling coil 5 and the coupling coil 6 each essentially functions as a bandpass filter, providing the necessary coupling coefficient and, consequently, the necessary transformation coefficient in the corresponding resonant transformer.
[0048] Thus, the slider 10 and the slider 11 substantially allow using not all the inductance of the coupling coil 5 and the coupling coil 6, respectively, in their operating modes, but only a certain portion thereof, depending on the desired task.
[0049] It should further be noted that each of the coupling coils 5, 6 and quarter-wave windings 1.1, 2.1 of the transformers has its own capacity or parasitic (linear) capacity, which increases with the increase of the number of turns and their design. In particular, there is an inter-turn capacitance between adjacent or neighboring turns, due to which some portion of the current passes through the capacitance between the turns, which leads to a decrease in the resistance between the terminals in each of the coupling coil 5, coupling coil 6, transformer winding 1.1 or transformer winding 2.1. This is due to the fact that the total voltage applied to the coupling coil 5, the coupling coil 6, the transformer winding 1.1 or the transformer winding 2.1 is essentially divided into inter-turn voltages, which causes the generation of an electric field between the turns, which causes the accumulation of charges, wherein the turns, separated by insulation layers, substantially form the plates of many small capacitors, through which a portion of the current flows and from the total capacity of which the self-capacitance of the coupling coil 5, the coupling coil 6, the transformer winding 1.1 or the transformer winding 2.1 is composed. Thus, the coupling coil 5, the coupling coil 6, the transformer winding 1.1 and the transformer winding 2.1 each have not only inductive properties, but also capacitive properties, which depend on the type of design and technical specifications thereof.
[0050] As shown in
[0051] Furthermore, as shown in
[0052] In the preferred embodiment of the present technical solution, the source 4 of electrical energy is one of the sources of alternating current provided in the prior art, which is configured to output or supply alternating current (AC) voltage to the coupling coil 5, and the receiver 7 of electrical energy is one of the receivers of alternating current electrical energy provided in the prior art, which is configured to consume or accumulate alternating current (AC) electrical energy output by the coupling coil 6 to said receiver 7.
[0053] In one of the embodiments of the present technical solution, the source 4 of electrical energy may be one of the prior art sources of alternating current electrical energy configured to output or supply alternating current (AC) voltage to the coupling coil 5, and the receiver 7 of electrical energy may be one of the prior art receivers of direct current electrical energy configured to consume or accumulate direct current (DC) electrical energy. In this embodiment, the source 4 of electrical energy may be connected directly to the coupling coil 5 on the side of the transmitting resonant transformer 1, and the electrical energy receiver 7 must be connected to the coupling coil 6 on the side of the receiving resonant transformer 2 by means of an alternating current to direct current converter (not shown), which converts alternating current electrical energy received from the coupling coil 6 into direct current electrical energy consumed by the electrical energy receiver 7.
[0054] In yet another embodiment of the present technical solution, the source 4 of electrical energy may be one of the prior art sources of direct current electrical energy, configured to output direct current (DC) voltage, and the receiver 7 of electrical energy may also be one of the prior art receivers of alternating current electrical energy, configured to consume or accumulate alternating current (AC) electrical energy. In this embodiment, the electrical energy source 4 must be connected to the coupling coil 5 on the side of the transmitting resonant transformer 1 by means of a direct current to alternating current converter (not shown), which converts direct current electrical energy output by the electrical energy source 4 into alternating current electrical energy supplied to the coupling coil 5, and the electrical energy receiver 7 may be connected directly to the coupling coil 6 on the side of the receiving resonant transformer 2.
[0055] In another embodiment of the present technical solution, the source 4 of electrical energy may be one of the prior art sources of direct current electrical energy, configured to output direct current (DC) voltage, and the receiver 7 of electrical energy may also be one of the prior art direct current (DC) electrical energy receivers configured to consume or accumulate direct current (DC) electrical energy. In this embodiment, the electrical energy source 4 must be connected to the coupling coil 5 on the side of the transmitting resonant transformer 1 by means of a direct current to alternating current converter (not shown), which converts the direct current electrical energy output by the electrical energy source 4 into alternating current electrical energy supplied to the coupling coil 5, and the electrical energy receiver 7 must be connected to the coupling coil 6 on the side of the receiving resonant transformer 2 by means of an alternating current to direct current converter (not shown), which converts alternating current electrical energy received from the coupling coil 6 into direct current electrical energy consumed by the electrical energy receiver 7.
[0056] As shown in
[0057] Thus, the slider 10 and the slider 11 each enable to adjust or tune the coupling coil 5 and the coupling coil 6, respectively, in particular, to adjust the number of turns thereof, which provides the setting of a desired coupling coefficient value, transformation coefficient (Q) value and bandwidth (if there are present reactive elements in the electrical energy source 4 and in the electrical energy receiver 7). It should be noted that changing the operating mode of the coupling coil 5 will lead to a change in internal resistance thereof, thus enabling to tune or adjust the coupling coefficient between the coupling coil 5 and the transformer winding 1.1 on the side of the transmitting resonant transformer 1, which have a magneto-inductive link between each other. Similarly, changing the operating mode of the coupling coil 6 will lead to a change in internal resistance thereof, thus enabling to tune or adjust the coupling coefficient between the coupling coil 6 and the transformer winding 2.1, which have a magneto-inductive link between each other, on the side of the receiving resonant transformer 2.
[0058] It should be noted that each of the coupling coil 5 and the coupling coil 6 may be made, for example, of turns of heavy copper wire, a copper tube (for example, a 6 mm copper tube or a large cross-section conductor) or a litz wire, wherein the number of turns of the coupling coil 5 or coil 6 is substantially less than that of the resonant transformer 1 and resonant transformer 2, respectively, as the resistance of the winding of the coupling coil 5 or the coupling coil 6 must be small in view of the possible flow of a large electrical current therethrough. Each of the quarter-wave winding 1.1 and quarter-wave winding 2.1 may have a length exceeding the diameter thereof by up to about 5 times or alternately may have a diameter exceeding the length thereof by up to about 5 times, wherein the diameter of the conductor for the winding is selected so as to, for example, obtain 1000 turns (in other embodiments of the present technical solution, each of the quarter-wave winding 1.1 and quarter-wave winding 2.1 may have from hundreds to thousands of turns). Each of the winding of the coupling coil 5 or coupling coil 6 may be made in the form of a flat spiral, a short helical winding, a conical winding or a concentrated winding.
[0059] It should also be noted that the coupling coil 5 and the coupling coil 6 substantially function as the primary winding in the resonant transformer 1 and the secondary winding in the resonant transformer 2, respectively, and the quarter-wave winding 1.1 and the quarter-wave winding 2.1 substantially function as the secondary winding in the resonant transformer 1 and the primary winding in the resonant transformer 2, respectively. As disclosed below, the primary and secondary windings in the resonant transformer 1 having a magneto-inductive link between each other form two interconnected oscillating circuits on the transmitting side in the system 100, and the primary and secondary windings in the resonant transformer 2 having a magneto-inductive link between each other form two interconnected oscillating circuits on the receiving side in the system 100 such that each of the resonant transformer 1 and resonant transformer 2 will not only efficiently transmit electrical energy from the primary winding thereof to the secondary winding thereof, providing the required output voltage at low currents, but also store electrical energy.
[0060] In particular, the coupling coil 5 has its inductance capable of resonating with the intrinsic (parasitic) capacitance of the coupling coil 5, which fact substantially allows the coupling coil 5 to function as a primary oscillating circuit or LC circuit (also referred to in the prior art as a tuned circuit or resonant circuit) on the transmitting side or on the side of the resonant transformer 1 in the system 100. Similarly, the coupling coil 6 has its inductance capable of resonating with the intrinsic (parasitic) capacitance of the coupling coil 6, which fact substantially allows the coupling coil 6 to function as a secondary oscillating circuit or LC circuit (also referred to in the prior art as a tuned circuit or resonant circuit) on the receiving side or on the side of the resonant transformer 2 in the system 100. It should be noted that the coupling coil 5 will substantially pump energy to the system 100, and the coupling coil 6 will substantially drain energy from the system 100.
[0061] Furthermore, the quarter-wave winding 1.1 has its linear inductance capable of resonating with the intrinsic (parasitic) capacitance of the winding, which fact substantially allows the quarter-wave winding 1.1 to function as a secondary oscillating circuit or LC circuit (also referred to in the prior art as a tuned circuit or resonant circuit) on the transmitting side or on the side of the resonant transformer 1 in the system 100. Similarly, the quarter-wave winding 2.1 also has its inductance capable of resonating with the intrinsic (parasitic) capacitance of the winding, which fact substantially allows the quarter-wave winding 2.1 to function as a primary oscillating circuit or LC circuit (also referred to in the prior art as a tuned circuit or resonant circuit) on the receiving side or on the side of the resonant transformer 2 in the system 100.
[0062] The primary oscillating circuit and the secondary oscillating circuit on the transmitting and receiving sides, i.e. on the side of the transmitting transformer 1 and on the side of the receiving transformer 2, in the system 100 are configured such that the primary oscillating circuit and the secondary oscillating circuit on the side of the transmitting transformer 1 resonate at the same frequency, i.e. have the same resonant frequency, and the primary oscillating circuit and the secondary oscillating circuit on the side of the receiving transformer 2 also resonate at the same frequency, i.e. have the same resonant frequency, wherein the resonant frequency on the side of the transmitting transformer 1 and the resonant frequency on the side of the receiving transformer 2 will substantially coincide or have the same values.
[0063] Thus, when the primary winding of the transmitting transformer 1 is fed with alternating current having a frequency equal to the resonant frequency of the secondary winding of said transformer 1, the voltage at the output of the transformer 1 may increase by tens or even thousands of times.
[0064] It should be noted that the movement of the slider 10 allows substantially not only to tune the input voltage on the transmitting transformer 1, but also to adjust the intrinsic (parasitic or linear) capacitance and inductance of the coupling coil 5 to ensure that the oscillation frequency of the primary oscillating circuit formed by the coupling coil 5 coincides with the resonant frequency of the secondary oscillating circuit formed by the quarter-wave winding 1.1.
[0065] Moving the sliding contact 8 along the quarter-wave winding 1.1 makes it possible to adjust (the adjustment including continuous or periodic adjustment) the ratio of turns between the secondary winding and the primary winding of the transmitting resonant transformer 1, which fact in turn enables to adjust the output voltage output by the transmitting resonant transformer 1 in very wide ranges at very small increments, obtaining an output voltage of alternating current of increased frequency. Furthermore, depending on the embodiment of the electrical energy source 4, moving the sliding contact 8 along the quarter-wave winding 1.1 allows substantially to pump the system 100 with providing the possibility of transmitting electrical energy from the transmitting resonant transformer 1 to the receiving resonant transformer 2 along the single-wire transmission line 3 disclosed below.
[0066] To excite the quarter-wave operation mode of the transmitting resonant transformer 1, the required wave resistance impedances are substantially also selected, which fact makes it possible to provide the required coupling coefficient between the coupling coil 5 functioning as the primary winding of the transmitting resonant transformer 1 and the winding 1.1 functioning as the secondary winding of the transmitting resonant transformer 1. Thus, to ensure proper operation of the transmitting side in the system 100, it is necessary to tune not only the frequency at which the transmitting resonant transformer 1 will operate, but also to tune the internal resistance in the system 100, wherein moving the sliding contact 8 between the high-potential and low-potential terminals of the winding 1.1 allows to adjust or select the operating frequency at which the transmitting resonant transformer 1 operates (in particular, moving the sliding contact 8 along the turns of the winding 1.1 towards the low-potential terminal thereof substantially results in an increased operating frequency of the transmitting resonant transformer 1, and moving the sliding contact 8 along the turns of the winding 1.1 towards the high-potential terminal thereof substantially results in a decreased operating frequency of the transmitting resonant transformer 1).
[0067] As shown in
[0068] It should be noted that the movement of the sliders 3.1 and 3.2 along the contact terminals 1.2, 2.2, respectively, also allows to select required parameters of the system 100: from high-potential to “medium-potential” and from “medium-potential” to low-potential, with different modes: traveling wave mode, standing wave mode and hybrid wave mode. The traveling wave mode is characterized by the presence of only an incident wave propagating from the transmitting system to the receiving system. There is no reflected wave present. The power born by the incident wave is completely released in the load. In this mode, BU=0, |H|=0, Rtw=Rsw=1. The traveling wave mode is formed when connecting the sliders 3.1 and 3.2 at a closer distance to the respective geometric centers of the windings 1.1, 2.1 in the resonant transformers 1 and 2. The standing wave mode is characterized by the fact that the amplitude of the reflected wave is equal to that of the incident wave BU=AU, i.e. the energy of the incident wave is completely reflected from the receiving system and returned back to the transmitting system. In this mode, |H|=1, Rsw=∞, Rtw=0. The standing wave mode is formed when connecting the sliders 3.1 and 3.2 at a closer distance to the corresponding low-potential terminals of the windings 1.1, 2.1 in the resonant transformers 1 and 2. In the hybrid wave mode, the amplitude of the reflected wave satisfies the condition 0<BU<AU, i.e. a portion of the power of the incident wave is absorbed by the receiving system, and the remaining portion in the form of a reflected wave is returned back, which repeats n times, the number of “n” repeats depends on the Q-factor of the entire system. Thereby, 0<|H|<1, 1<Rsw<∞, 0<Rtw<1. The hybrid wave mode is formed when connecting the sliders 3.1 and 3.2 substantially between the corresponding low-potential terminals and the geometric centers of the windings 1.1, 2.1 in the resonant transformers 1 and 2.
[0069] When increasing the length or distance of the electrical power transmission line 3, there is typically observed a decrease in the frequency of the electrical current flowing through the electrical power transmission line 3, but due to the proper tuning of said frequency with providing the preservation of the wave effect in the system 100 and connection of the electrical power transmission line 3 to the low-potential portions of the windings 1.1, 2.1, there will be no significant frequency change when increasing the distance between the transmitting and receiving resonant transformers 1, 2 when transmitting electrical energy via the electrical energy transmission line 3, i.e. the frequency will not depend on the length or distance of the electrical energy transmission line 3.
[0070] When the electrical energy transmitted via the electrical energy transmission line 3 from the transmitting resonant transformer 1 to the receiving resonant transformer 2 feeds the primary winding of the receiving transformer 2, the primary winding being the quarter-wave winding 2.1, with an alternating electrical current having a frequency equal to the resonant frequency of the secondary oscillatory circuit of the transmitting resonant transformer 1 defined by the quarter-wave winding 1.1, which results in the excitation of resonant oscillations in the primary oscillatory circuit of the receiving transformer 2 defined by the quarter-wave winding 2.1 that is substantially the primary winding of the receiving transformer 2.
[0071] The movement of the sliding contact 9 along the quarter-wave winding 2.1 makes it possible to adjust (including continuously or periodically) the ratio of turns between the primary and secondary windings of the receiving resonant transformer 2, which in turn allows to adjust the voltage at the receiving resonant transformer 2 in very wide ranges and at very small increments, wherein the voltage at the output of the receiving resonant transformer 2 will also substantially consist of a high frequency sinusoidal alternating current.
[0072] It should be noted that the movement of the slider 11 substantially allows not only to tune the input voltage supplied to the electrical energy receiver 7, but also to adjust the intrinsic (parasitic or linear) capacitance and inductance of the coupling coil 6 with providing the required wave resistance of the secondary oscillatory circuit defined by the coupling coil 6 that is substantially a secondary winding of the receiving resonant transformer 2, coinciding with the resonant frequency of the primary oscillatory circuit defined by the quarter-wave winding 2.1.
[0073] To excite the quarter-wave operation mode of the receiving resonant transformer 2, the required wave resistance impedances are substantially also selected, which fact makes it possible to provide the required coupling coefficient between the winding 2.1 functioning as a primary winding of the receiving resonant transformer 2 and the coupling coil 6 functioning as a secondary winding of the receiving resonant transformer 2. Thus, to ensure proper operation of the receiving side in the system 100, it is necessary to tune not only the frequency at which the receiving resonant transformer 2 will operate, but also to tune the internal resistance in the system 100, wherein moving the sliding contact 9 between the high-potential and low-potential terminals of the winding 2.1 allows to adjust or select the operating frequency at which the receiving resonant transformer 2 operates (in particular, moving the sliding contact 9 along the turns of the winding 2.1 towards the low-potential terminal thereof substantially results in an increased operating frequency of the receiving resonant transformer 2, and moving the sliding contact 9 along the turns of the winding 2.1 towards the high-potential output thereof substantially results in a decreased operating frequency of the receiving resonant transformer 2), as well as electrical energy transmission modes (see note 1).
[0074] Thus, as follows from the above description of the operating peculiarities of the transmitting and receiving sides in the system 100 shown in
[0075]
[0076] It should be noted that each of the solitary capacitors 12, 13 in the system 200 may be made in the form of a smooth metal sphere or torus having curvilinear surfaces of a large area, which fact allows same to reduce the potential (electrical field) gradient at the high-potential terminal of the corresponding one of the quarter-wave windings 1.1, 2.1 of the transformer. Each of the solitary capacitors 12, 13 in the system 200 functions similarly to the corona ring, increasing the voltage threshold at which air discharges are produced, such as corona discharge and brush discharge. Thus, the suppression of premature air breakdown and the reduction of energy loss provided by each of the solitary capacitors 12, 13 in the system 200 makes it possible to increase the Q-factor of the transmitting and receiving resonant transformers 1, 2, respectively, as well as to increase the output voltage thereof at waveform peaks. In one of the embodiments of the present technical solution, a torus made of corrugated aluminum and having an outer diameter equal to or greater than the diameter of the quarter-wave winding 1.1 or the quarter-wave winding 2.1 may be used as each of the solitary capacitors 12, 13 in the system 200.
[0077] Furthermore, another significant difference between the system 200 and the above system 100 above is that, in the system 200, the linear inductance possessed by the quarter-wave winding 1.1 is capable of resonating with the total linear parasitic capacitance, which is the sum of the intrinsic (parasitic) capacitance of the winding and the capacitance of the solitary capacitor 12, which fact substantially allows the quarter-wave winding 1.1 to function as a secondary oscillatory circuit or LC circuit (also referred to in the prior art as a tuned circuit or resonant circuit) on the transmitting side or the side of the resonant transformer 1 in the system 200, and the linear inductance possessed by the quarter-wave winding 2.1 is capable of resonating with the total linear parasitic capacitance, which is the sum of the intrinsic (parasitic) capacitance of the winding and the capacitance of the solitary capacitor 13, which fact substantially allows the quarter-wave winding 2.1 to function as a primary oscillating circuit or LC circuit (also referred to in the prior art as a tuned circuit or resonant circuit) on the receiving side or the side of the resonant transformer 2 in the system 200.
[0078] The solitary capacitor 12 in the system 200 will substantially (insignificantly) facilitate the reduction of the resonance frequency on the secondary winding of the transmitting resonant transformer 1. In one of the embodiments of the present technical solution, a torus made of corrugated aluminum and having an outer diameter equal to or greater than the diameter of the quarter-wave winding 1.1 or the quarter-wave winding 2.1 may be used as each of the solitary capacitors 12, 13. The capacitance of the solitary capacitor 12 may substantially be set depending on the required power and parameters of the transmitting resonant transformer 1.
[0079] The solitary capacitor 13 in the system 200 will substantially facilitate the reduction of the resonance frequency on the primary winding of the transmitting resonant transformer 1, the primary winding being defined by the winding 2.1. In one of the embodiments of the present technical solution, a torus made of corrugated aluminum and having an outer diameter equal to or greater than the diameter of the quarter-wave winding 1.1 or the quarter-wave winding 2.1 may be used as each of the solitary capacitors 12, 13. The capacitance of the solitary capacitor 13 may substantially be set depending on the required power and parameters of the receiving resonant transformer 2.
[0080]
[0081] In one of the embodiments of the system 300 for transmitting electrical energy, shown in
[0082] In another embodiment of the system 300 for transmitting electrical energy, shown in
[0083]
[0084]
TABLE-US-00001 TABLE 1 Results of tests with respect to diagrams according to FIG. 5-11 F, Uin, Iin, Uload, Iload, Ilin, Ulin, U1, U2, INDICATORS Diagram kHz V A V mA mA V kV kV P1 P2 EFFICIENCY FIG. 5 53.70 19.30 1.42 18.90 923 115 266 3.7 5.2 27.41 17.4 0.64 59.20 13.20 2.30 13.10 763 36 850 7.7 3.5 30.36 10.0 0.33 54.00 19.30 1.42 18.90 923 115 266 3.7 5.2 27.41 17.4 0.64 57.00 13.20 2.30 13.10 763 36 850 7.7 3.5 30.36 10.0 0.33 FIG. 6 56.70 18.00 0.62 7.61 630 60 180 2.9 4.4 11.16 4.8 0.43 60.20 18.50 2.45 9.08 640 33 970 8.8 4.3 45.33 5.8 0.13 FIG. 7 59.10 28.60 0.45 3.55 450 57 100 6.0 3.5 12.87 1.6 0.12 61.00 16.40 2.70 5.90 537 51 1022 9.2 4.2 44.28 3.2 0.07 117.70 17.00 2.70 13.10 730 155 180 0.1 0.1 45.90 9.6 0.21 FIG. 8 59.90 11.20 2.70 0.60 170 77 1032 6.0 2.5 30.24 0.1 0.00 84.10 17.80 1.75 10.95 663 125 914 1.2 0.1 31.15 7.3 0.23 FIG. 9 54.40 12.60 2.70 1.45 347 111 1038 3.6 1.0 34.02 0.5 0.01 74.20 20.00 0.50 4.68 492 80 380 2.0 0.1 10.00 2.3 0.23 FIG. 10 46.30 15.90 1.50 4.00 363 91 1300 1.5 0.2 23.85 1.5 0.06 FIG. 11 42.10 15.30 2.10 4.00 400 98 1350 1.2 0.2 32.13 1.6 0.05
[0085]
TABLE-US-00002 TABLE 2 Results of testing with respect to diagrams according to FIG. 12-21 F, Uin, Iin, Uload, Iload, Ilin, Ulin, U1, U2, INDICATORS Diagram kHz V A V mA mA V kV kV P1 P2 EFFICIENCY FIG. 12 55.00 28.30 0.70 10.50 1.44 33 136 3.5 2.2 19.81 15.1 0.76 59.00 23.00 1.40 15.00 1.74 37 266 3.0 4.1 32.20 26.1 0.81 FIG. 13 56.50 28.30 0.70 10.50 1.44 33 136 3.5 2.2 19.81 15.1 0.76 56.90 26.30 1.28 17.30 1.90 37 266 3.8 3.9 33.66 32.9 0.98 57.40 27.50 1.10 16.20 1.83 38 200 4.1 4.1 30.25 29.6 0.98 58.10 23.00 1.30 16.00 1.80 35 220 3.5 4.2 29.90 28.8 0.96 58.90 23.00 1.40 15.00 1.74 37 266 3.0 4.1 32.20 26.1 0.81 62.60 27.00 1.40 12.00 1.55 33 600 6.5 4.6 37.80 18.6 0.49 FIG. 14 60.90 24.50 1.30 16.80 1.82 37 240 3.0 3.8 31.85 30.6 0.96 65.50 19.00 1.60 11.50 1.50 34 510 6.2 3.8 30.40 17.3 0.57 FIG. 15 64.10 22.50 1.00 13.60 1.60 36 214 2.6 3.1 22.50 21.8 0.97 67.80 19.10 1.60 11.90 1.55 44 385 5.6 3.4 30.56 18.4 0.60 FIG. 16 67.10 23.70 0.85 12.90 1.52 38 163 3.0 2.5 20.15 19.6 0.97 71.00 22.20 1.45 11.70 1.54 40 350 4.6 3.0 32.19 18.0 0.56 FIG. 17 72.40 27.60 1.05 15.20 1.78 38 195 2.8 2.2 28.98 27.1 0.93 77.30 20.00 1.30 11.20 1.48 49 279 3.7 1.5 26.00 16.6 0.64 FIG. 18 77.60 30.40 0.98 15.80 1.70 49 175 2.5 1.5 29.79 26.9 0.90 85.50 24.40 1.30 10.80 1.50 59 251 1.2 3.6 31.72 16.2 0.51 FIG. 19 72.40 29.30 1.10 13.70 1.67 53 169 4.4 1.0 32.23 22.9 0.71 75.30 20.70 1.65 14.40 1.72 57 146 3.8 1.1 34.16 24.8 0.73 FIG. 20 76.20 40.00 0.55 6.80 1.28 50 78 4.8 3.2 22.00 8.7 0.40 77.20 37.60 0.75 10.90 1.60 42 168 3.7 3.9 28.20 17.4 0.62 FIG. 21 72.40 43.50 0.95 9.65 1.33 62 330 6.0 3.0 41.33 12.8 0.31 70.80 37.00 0.75 9.70 1.44 47 199 4.0 5.4 27.75 14.0 0.50
[0086]
TABLE-US-00003 TABLE 3 Results of testing with respect to diagrams according to FIG. 22-24 F, Uin, Iin, Uload, Iload, Ilin, Ulin, U1, U2, INDICATORS Diagram kHz V A V mA mA V kV kV P1 P2 EFFICIENCY FIG. 22 67.00 19.00 1.86 12.70 1.57 156 179 0.1 0.1 35.34 19.9 0.56 93.00 35.00 1.00 14.70 1.65 72 199 0.1 0.1 35.00 24.3 0.69 FIG. 23 63.00 29.50 1.80 20.00 2.00 209 265 2.5 1.0 53.10 40.0 0.75 88.00 32.00 0.75 11.50 1.47 63 175 0.3 0.1 24.00 16.9 0.70 FIG. 24 60.10 32.00 2.10 20.90 2.03 226 273 3.0 1.0 67.20 42.4 0.63 77.90 40.00 1.20 13.80 1.60 84 183 0.3 0.2 48.00 22.1 0.46
[0087] The results of testing with respect to the diagrams of