Method and device for crosstalk compensation

Abstract

There is disclosed a method for eliminating an added crosstalk signal from a measured data signal, which is generated by an image current. There is further disclosed a signal processing unit for carrying out the method. There is still further disclosed a mass spectrometer and a mass analyser comprising the signal processing unit for carrying out the method. There is yet still further disclosed a Fourier transform mass spectrometer configured to eliminate the added crosstalk signal from a measured data signal.

Claims

1. A Fourier transform mass spectrometer comprising: (a). a detector unit adapted to detect a measured data signal that comprises an image-current signal generated by motions of ions between electrostatic electrodes of an electrostatic trap mass analyzer; (b). a source of electromagnetic disturbance that is outside of the electrostatic trap mass analyzer, wherein the electromagnetic disturbance interacts with the detector unit by crosstalk, resulting in the measured data signal comprising an added crosstalk signal; (c). an extraction device adapted to extract a decoupled disturbance signal from the source of electromagnetic disturbance; (d). a conditioning module adapted to condition the decoupled disturbance signal by applying a phase shift and/or an amplitude amplification to obtain a compensation signal; (e). a control unit that is configured to control calibration parameters and control parameters of the conditioning module; and (f). an adding module, adapted to superpose the measured data signal and the compensation signal; wherein the phase shift and/or amplitude amplification applied by the conditioning module cause(s) the compensation signal to correspond to an inverted crosstalk signal that, when superimposed upon the measured data signal by the adding module, essentially eliminates the added crosstalk signal from the measured data signal.

2. A Fourier transform mass spectrometer according to claim 1, wherein the adding module further comprises a junction to which the adding module is adapted to supply both the measured data signal and the compensation signal in order to superpose them.

3. A Fourier transform mass spectrometer according to claim 1 further comprising a signal processing unit comprising: (i). the conditioning module; (ii). the adding module; (iii). a data signal input line adapted to receive the measured data signal from the detector unit; (iv). a disturbance signal input line adapted to receive the decoupled disturbance signal from the extraction device; and (v). an output line adapted to supply the compensation signal to at least one data receiving device.

4. A Fourier transform mass spectrometer according to claim 3, wherein the signal processing unit further comprises: one or more additional disturbance signal input lines, each additional disturbance signal input line adapted to receive a respective additional decoupled disturbance signal from the extraction device, wherein each additional decoupled disturbance signal is derived from a respective additional source of electromagnetic disturbance, each such electromagnetic disturbance interacting with the detector unit by crosstalk.

Description

BRIEF DESCRIPTION OF THE DRAWINGS

(1) The drawings, described below, are for illustration purposes only. The drawings are not intended to limit the scope of the present teaching in any way.

(2) FIG. 1 exemplifies a block scheme presenting a method according to an embodiment of the invention;

(3) FIG. 2 exemplifies a schematic view of a signal processing unit according to an embodiment of the invention;

(4) FIG. 3A shows a schematic view of an embodiment of an arrangement of signal processing components configured to execute the inventive method;

(5) FIG. 3B shows a more detailed schematic view of an embodiment of an arrangement of signal processing components configured to execute the inventive method;

(6) FIG. 3C shows a more detailed schematic view of an embodiment of an arrangement of signal processing components configured to execute the inventive method;

(7) FIG. 4A shows a schematic view of an inverter, which can be used in an arrangement of signal processing components to execute to the inventive method, in particular in the arrangement of FIG. 3C;

(8) FIG. 4B shows a more detailed schematic view of the inverter of FIG. 4A;

(9) FIG. 5 shows a schematic view of a phase shifter, which can be used in an arrangement of signal processing components to execute to the inventive method, in particular in the arrangement of FIG. 3C;

(10) FIG. 6 shows a schematic view of an amplifier, which can be used in an arrangement of signal processing components to execute to the inventive method, in particular in the arrangement of FIG. 3C;

(11) FIG. 7 shows a schematic embodiment of a adding module, which can be used in an arrangement of signal processing components to execute the inventive method, in particular in the arrangement of FIG. 3C;

(12) FIG. 8A shows an embodiment of an extraction device, adapted to extract a decoupled disturbance signal from a source of electromagnetic disturbance.

(13) FIG. 8B shows another embodiment of an extraction device, adapted to extract a decoupled disturbance signal from a source of electromagnetic disturbance.

(14) FIG. 8C shows further embodiments of extraction devices, adapted to extract a decoupled disturbance signal from a source of electromagnetic disturbance;

(15) FIGS. 9A-9F depict exemplary embodiments of the data signal obtained before and after using the present method of crosstalk signal elimination;

(16) FIGS. 10A-10D depict an exemplary embodiment of calibrating control parameters of the conditioning module 115 for eliminating the crosstalk signal.

DETAILED DESCRIPTION

(17) In the following, exemplary embodiments of the invention will be described, referring to the figures. These examples are provided to provide further understanding of the invention, without limiting its scope.

(18) In the following description, a series of features and/or steps are described. The skilled person will appreciate that unless required by the context, the order of features and steps is not critical for the resulting configuration and its effect. Further, it will be apparent to the skilled person that irrespective of the order of features and steps, the presence or absence of time delay between steps or simultaneous implementation, can be present in some or all of the described steps.

(19) FIG. 1 shows a block scheme schematically describing the steps of the inventive method. A description of the method follows with also reference to FIGS. 3A, 3B, 3C for the components that can be used to implement the method.

(20) The method can be applied to a system comprising a detector unit 200 adapted to output a measured data signal 20, which is preferably by an image current. In particular, the method can be used with systems such as Fourier transform mass spectrometers, like ion cyclotron resonance mass spectrometers (ICR mass spectrometers, ICR-MS) and mass spectrometers using ion trapping, like Orbitrap® mass spectrometers offered by Thermo Fisher Scientific (Bremen) GmbH and Thermo Fisher Scientific Inc.

(21) In systems comprising such detector units, sources of an electromagnetic disturbance 100 may be present. Such sources of an electromagnetic disturbance 100 can be electronic devices like quadrupole electrode, the RF voltage supply of quadrupole electrodes, vibrations of vacuum pumps and other supplied RF voltages, e.g. of ion optics, AC/DC converter. Such devices emit an electromagnetic disturbance signal 102 (also referred to as an added crosstalk signal 102), for example electromagnetic radiation, which can unintentionally interact with the detector unit 200. Such interaction is generally known as crosstalk of the electromagnetic disturbance signal 102 and the detector unit 200. The crosstalk is modifying the measured data signal 20 in comparison to an undisturbed measured signal (which would be hypothetically measured in the absence of this interaction). It was found that due to the crosstalk of the electromagnetic disturbance signal 102 with a detector unit 200, which is detecting a measured data signal 20 generated by an image current, an added crosstalk signal is superposed to the undisturbed measured signal. For many sources of an electromagnetic disturbance 100, the added crosstalk signal is a periodic signal, which is interfering with the undisturbed measured signal. In particular, due to such added cross talk signals, the following effects can occur in the measured data signal 20: additional harmonics, phase shifts, destructive interference, beats, and standing waves. The present method describes a way to compensate such undesirable added crosstalk signals in order to obtain a compensated data signal 22. The method can, for example, be used in the field of Fourier transform mass spectroscopy with the detector unit 200 being a part of the mass spectrometer. As a concrete example, the method can be used with an Orbitrap® mass analyser in order to filter out undesirable added crosstalk signals. Such added crosstalk signals can originate, for example, from quadrupole electrodes, generators supplying the RF voltage to quadrupole electrodes (such as electrodes of quadrupole mass filters) or from components of the detector unit 200 and/or electronics in the surrounding of the detector unit 200.

(22) The method can comprise step S1 of extracting a decoupled disturbance signal 10. The decoupled disturbance signal 10 can originate from any source of electromagnetic disturbance 100, and can be extracted by an extraction device 103. The electromagnetic disturbance originated from such a source of electromagnetic disturbance can interact with the detector unit 200 by crosstalk. Due to this, an added crosstalk signal is added by superposition to an undisturbed measured data signal, which would be detected by the detector unit 200, if the source of disturbance 100 would be absent or not active. The interaction is resulting in the measured data signal 20 comprising the added crosstalk signal. Therefore, the crosstalk between the electromagnetic disturbance signal 102 emitted by the source of electromagnetic disturbance 100 and the detector unit 200 is influencing the measured data signal 20.

(23) The effect of crosstalk can be eliminated by using the decoupled disturbance signal to adjust the measured data signal 20 in order to obtain a compensated data signal 22. The effect of crosstalk is then eliminated, when the influence of an added crosstalk signal on the compensated data signal 22 is so small, that it is irrelevant when supplied to a data-receiving device. This means that the remaining influence of an added crosstalk signal on the compensated data signal 22 is so small, that for information derived from the compensated signal supplied to the data receiving device, no other result was derived, then the one that would be derived from an undisturbed measured data signal. In other words, the added crosstalk signal is eliminated when information derived from the compensated signal 22 is not influenced by the presence of the source of an electromagnetic disturbance 100 and the associated crosstalk. For example, in a Fourier transform mass spectrometer, any identified mass peak caused by a source of an electromagnetic disturbance 100 and not by detected ions is eliminated. There might be specific criteria, which can be used to define when a mass peak is identified. Examples of such criteria are already described before. For example, the remaining influence of an added crosstalk signal might be small enough, if its amplitude is significantly reduced. The amplitude may be reduced so much, that it is below five times of the medium amplitude of a measured noise signal, preferably below three times of the medium amplitude of a measured noise signal and in particular below two times of the medium amplitude of a measured noise signal. On the other hand, the remaining influence of an added crosstalk signal might be small enough, if the phase shift between the added crosstalk signal and the compensation signal 16 deviates only very little from 180°, when both signals are supplied to the same junction in an adding module 220. Typically, the value of the deviation from 180° is below 2°, preferably below 1° and more preferably below 0.5°. The extracting of the decoupled disturbance signal 10 can be achieved by extraction device 103, which is adapted to receive the decoupled disturbance signal 10 from the source of electromagnetic disturbance 100. The added crosstalk signal 102 (also referred to as an electromagnetic disturbance signal 102) of a source of electromagnetic disturbance 100 and its corresponding decoupled disturbance signal 10 comprise at least nearly exactly the same shape, but might have a different amplitude and/or might be phase shifted with respect to each other. Usually, the added crosstalk signal 102 of a source of electromagnetic disturbance 100 and its corresponding decoupled disturbance signal 10 are periodic functions. Then they have the same period T, frequency f and angular frequency ω. Obtaining the compensated data signal 22 therefore can require adjusting the decoupled disturbance signal 10 by conditioning before using it to adjust the measured data signal 20.

(24) Therefore, in step S2, the decoupled disturbance signal 10 can be conditioned to obtain an appropriate compensation signal 16. This is done by applying a phase shift and/or amplitude amplification to the decoupled disturbance signal 10 to match or approach the amplitude and/or phase of the inverted added crosstalk signal 102 of the measured data signal 20. This is explained in more detail with reference to FIGS. 3A, 3B, 3C.

(25) In step S3, the measured data signal 20 and the compensation signal 16 are provided to an adding module 220. In the adding module 220, both signals, are superposed, e.g. by supplying to one junction. By superposition of both signals, a compensated data signal 22 is generated, which can be supplied to a data-receiving device. In this way, a compensated data signal 22 can be obtained.

(26) The conditioning module has to condition the decoupled disturbance signal 10 to obtain an appropriate compensation signal 16 in such a way that, when the measured data signal 20 and compensation signal 16 are superposed, the compensation signal 16 corresponds to an essentially inverted signal of the added crosstalk signal. This condition is satisfied when the amplitudes and phase shift of both signals only deviate so much, that the added crosstalk signal does not have a relevant influence on the compensated data signal 22 when it is supplied to a data-receiving device. Details about the acceptable amplitude deviation and phase deviation are described before.

(27) Preferably, the conditioning module has to condition the decoupled disturbance signal 10 to obtain an appropriate compensation signal 16 in such a way that, when the measured data signal 20 and compensation signal 16 are superposed, the compensation signal 16 corresponds to the inverted added crosstalk signal.

(28) The method can be performed continuously while the detector unit 200 generates the measured data signal 20. The electromagnetic disturbance signal 102 emitted by a source of an electromagnetic disturbance 100 may depend on time, the temperature and other parameters like a frequency of the source of an electromagnetic disturbance 100. The inventive method works independently of the temperature and other parameters like a frequency of the source of an electromagnetic disturbance 100 or time, and is therefore a very robust method. This is due to the effects of various parameter changes affecting the added crosstalk signal and the decoupled disturbance signal in the same way. In this way, the measured data signal 20 can be adjusted in real time or almost in real time to obtain the compensated data signal 22.

(29) FIG. 2 shows a schematic example of a signal-processing unit 1 according to an embodiment of the invention. The signal-processing unit 1 can be adapted to physically compensate the added crosstalk signal induced by the electromagnetic disturbance comprised in the measured data signal 20 (not shown here).

(30) The signal-processing unit 1 can comprise signal processing electronics 6, data signal input line 2, disturbance signal input line 3, and output line 4. The data signal input line 2 can be adapted to connect the device 1 to a detector unit 200 (not shown here) such as a Fourier transform mass analyser, said detector unit 200 producing a measured data signal 20. The disturbance signal input line 3 can be adapted to receive input from an extraction device (not shown here) that can respectively extract it from a source of electromagnetic disturbance 100. Such input is in the form of decoupled disturbance signal 10. FIG. 2 shows several disturbance signal input lines 3 receiving several different decoupled disturbance signals 10, 10′, 10″. This can be particularly advantageous in case several different sources of electromagnetic disturbance 100 are interfering with the measured data signal 20 via crosstalk. Using multiple disturbance signal input lines 3 allows for the multiple decoupled disturbance signals 10, 10′, 10″ to be obtained and then later the accordingly added crosstalk signals filtered out from the measured data signal 20 (not shown here). The decoupled disturbance signals 10, 10′, 10″ can be derived directly from the sources of the electromagnetic disturbance 100 via an extraction device 103. These extraction devices are discussed in more detail in relation to FIGS. 8A, 8B and 8C. The signal-processing device 1 can be adapted to receive the decoupled disturbance signals 10, 10′, 10″ originating from various sources of electromagnetic disturbance 100. The signal processing device 1 can be adapted to adjust said decoupled disturbance signals 10, 10′, 10″ so that they can be added to the measured data signal 20 to obtain a substantially crosstalk-free data signal, referred to as a compensated data signal 22. The output signal on the output line 4 can be adapted to connect the signal-processing device 1 to data reading devices, for example, an Analog-to-Digital converter. The compensated data signal 22 can then be transferred to data reading devices via the output line or lines 4. Thus, the signal-processing device 1 can be adapted to transfer a filtered data signal to a data-reading device via the output lines 4, allowing further visualization, processing and/or storing of the filtered signal, from which added crosstalk signals have been eliminated. Signal processing electronics 6 are discussed in more detail in relation to FIGS. 3A, 3B, 3C.

(31) FIG. 3A shows a simplified schematic view of components configured to execute the inventive method according to the present disclosure. A detector unit 200 generates a measured data signal 20. Due to the interaction, e.g. be interference between the detector unit 200 and an electromagnetic disturbance signal 102 emitted by a source of electromagnetic disturbance, the measured data signal 20 includes an unwanted added crosstalk signal 102.

(32) An extraction device 103 is configured to extract a decoupled disturbance signal 10 from the source of electromagnetic disturbance 102. This decoupled disturbance signal 10 comprises the same general shape and angular frequency as the added crosstalk signal 102, but may comprise a different amplitude and/or phase. The decoupled disturbance signal 10 is then input to a conditioning module 115, which is configured to adjust it to obtain a compensation signal 16. The compensation signal 16 is an input to an adding module 220, where the measured data signal 20 is also an input. The two signals are superposed, e.g. at one junction. The compensation signal 16 is conditioned in such a way, that it is an essentially inverted signal of the added crosstalk signal 102. Therefore, when the measured data signal 20 and the compensation signal 16 are superposed, the added crosstalk signal 102 is at least so far cancelled, that for information derived from the compensated signal 22 supplied to a data receiving device, no other result was derived, than the one that would be derived from an undisturbed measured data signal.

(33) The compensated data signal 22 is then sent to a control unit 240. The control unit 240 is configured to receive the compensated data signal 22. In the case of Fourier transform mass spectrometry, the control unit 240 is further configured to display the mass spectrum after the applied Fourier transform. It can be further configured to control the conditioning module 115. Furthermore, the control unit 240 can control the calibration of the control parameters of the conditioning module. The control unit 240 can further trigger the calibration of the control parameters.

(34) The signal-processing unit 1 consists of the adding module 220 and the conditioning module 115.

(35) FIG. 3B shows a slightly more detailed schematic view of signal processing electronics 6 according to one embodiment of the invention. A source of electromagnetic disturbance 100 can interfere with a detector unit 200 outputting a measured data signal 20 via an electromagnetic disturbance signal 102. Put differently, the electromagnetic disturbance signal 102 originating from a source of electromagnetic disturbance 100 can undesirably interact with the measured data signal 20. The present device illustrates a device adapted to eliminate an added crosstalk signal induced by such electromagnetic disturbance signal 102 from the measured data signal 20 to obtain a compensated data signal 22.

(36) A decoupled disturbance signal 10 can be obtained from a source of electromagnetic disturbance 100 by an extraction device 103. Possible ways of obtaining the decoupled disturbance signal 10 are discussed in relation to FIGS. 8A, 8B and 8C. The decoupled disturbance signal 10 undergoes a series of phase shifts via a phase shifter 170. The decoupled disturbance signal 10 can first travel to an inverter 120. The inverter 120 can be adapted to apply a substantially 180-degree phase shift to the decoupled disturbance signal 10 in order to “invert” it and yield an inverted decoupled disturbance signal 12. The inverted decoupled disturbance signal 12 can travel to a first phase shifter 140, followed by a second phase shifter 142. The first phase shifter 140 can be adapted to make coarse phase tuning of the inverted decoupled disturbance signal 12. The second phase shifter 142 can be adapted to make fine phase tuning of the inverted decoupled disturbance signal 12. The phase shifters 140, 142 can then output a modified decoupled disturbance signal 14. The phase shifters 120, 140, 142 can together form one 360°-phase shifter with fine adjustment steps. In different embodiments, the 360°-phase shifter can be made in the form of three phase shifters as shown or in the form of one or two, or any other amount of phase shifters without limiting the scope of the present invention. The inverter 120 and the phase shifters 140, 142 can be digitally controlled.

(37) The modified decoupled disturbance signal 14 can then be guided to an amplifier 160. The amplifier 160 can be adapted to adjust the amplitude of the modified decoupled disturbance signal 14 to make it equal to the amplitude of added crosstalk signal incorporated into the measured data signal 20. This amplitude can be estimated, for example, based on the expected peak shape of the measured data signal 20 versus the obtained shape. Additionally or alternatively, the amplitude of the added crosstalk signal can be estimated based on calibration procedures performed without a sample. That is, a data acquisition session on a Fourier transform mass spectrometer can be run without an active sample the composition of which is to be determined. In this way, the obtained signal would comprise no data, but rather only the added crosstalk signal, which can then be measured and compensated for. The amplitude of the modified decoupled disturbance signal 14 can be changed in one or more steps or by iteratively observing the measured data signal 20 or signals derived from it. In particular, when a Fourier transform is applied to the measured data signal, the amplitude of peaks in a mass spectrum that are induced by the electromagnetic disturbance 102 can be observed. The amplifier 160 can then output a compensation signal 16. The amplifier 160 can be digitally controlled.

(38) The phase shifter 170 comprising the inverter 120 and the phase shifters 140, 142, as well as the amplifier 160 are arranged in the conditioning module 115.

(39) The compensation signal 16 can then be guided to an adding module 220. The adding module 220 can be adapted to superpose the compensation signal 16 to the measured data signal 20, which might be pre-amplified in order to subtract the added crosstalk signal from the measured data signal 20. The adding module 220 can output a compensated data signal 22.

(40) The measured data signal 20 can have been pre-amplified by means of a pre-amplifier 150. The amplifier 150 can be adapted to be switched on or off in order to observe the measured data signal 20. It can be used when otherwise the measured data signal 20 would be low or when a user deems it convenient and/or necessary.

(41) FIG. 3C shows a more detailed schematic view of signal processing electronics 6 according to one aspect of the invention where a source of electromagnetic disturbance 100 can be, for example, a quadrupole-RF-supply for a mass spectrometer. The mass spectrometer can comprise a detector unit 200. The detector unit 200 can comprise two outer electrodes 201 of an Orbitrap® mass analyser and a pre-amplifier 150. As discussed in relation to FIG. 3B, the detector unit 200 can output a measured data signal 20 that comprises an added crosstalk signal. The shape of electromagnetic disturbance signal 102 can be extracted from the source of electromagnetic disturbance 100 by a decoupled disturbance signal 10 via an extraction device 103. This signal can be adapted conditioned and superposed to the measured data signal 20 to modify the measured data signal 20 to obtain a substantially crosstalk-free data signal, a compensated data signal 22.

(42) As described in relation to FIG. 3B, the decoupled disturbance signal 10 can travel to an inverter 120 resulting in an inverted decoupled disturbance signal 12. The inverted decoupled disturbance signal 12 can travel through first and second phase shifters 140, 142 to emerge as a modified decoupled disturbance signal 14. The modified decoupled disturbance signal 14 can travel through an amplifier 160 and come out as a compensation signal 16. This signal can then travel to a adding module 220 to be superposed to the measured data signal 20 The adding module 220 can output the compensated data signal 22.

(43) In FIG. 3C, the complete signal acquisition path with crosstalk canceling components is demonstrated on the example of a quadrupole as a source of an electromagnetic disturbance 100. Source 100, electromagnetic disturbance signal 102, measured data signal 20, pre-amplifier 150, outer electrodes 201 of an Orbitrap® mass analyser are parts of a hitherto existing configuration typically used in Orbitrap® mass spectrometers. Extracting module 103, decoupled disturbance signal 10, inverter 120, inverted decoupled disturbance signal 12, first phase shifter 140, second phase shifter 142, modified decoupled disturbance signal 14, amplifier 160, compensation signal 16, and compensated data signal 22 are additional components, which perform the elimination of the added crosstalk signal 102 induced by the source of an electromagnetic disturbance 100.

(44) The extraction module 103 is described in detail with reference to FIGS. 8A-8C. This device extracts the decoupled disturbance signal 10 from the source of the disturbance. This signal is provided to the conditioning module 115, which in this implementation comprises several stages of phase shifters 120, 140 and 142 shown in FIG. 4 and FIG. 5. The phase shifters assure the possibility to manipulate the phase in the full range of 0 . . . 360° in steps of sufficient resolution. Further, it comprises an amplifier 160 shown on FIG. 6 and an analogue adding module 220 shown on FIG. 7.

(45) FIG. 4A shows a simplified schematic illustration of the invertor 120 which can be digitally controlled. The decoupled disturbance signal 10 enters the invertor 120. Depending on the signal of the digital switch 123, the output can remain the same (“signal 0”), or be shifted by 180° (“signal 1”). This is illustrated in the figure by schematic signal representations. An inverted decoupled disturbance signal 12 can then, depending on the signal of the switch 123, exit the invertor 120.

(46) FIG. 4B shows a schematic exemplary electrical circuit of the invertor 120 which can be digitally controlled and can be adapted to apply a phase shift of 0° or 180° to a decoupled disturbance signal 10. The invertor 120 can be adapted to apply a phase shift by means of inverter circuitry 122 and output an inverted decoupled disturbance signal 12.

(47) In the used embodiment described in FIG. 4B, it is decided by a digital control switch 123 (signal 0/1), which shift is performed. The digital control switch activates one of two signal operational amplifiers 312 and 314, which are fed by each other with inverted signals derived from a transformer 308 having a primary electromagnetic coil 306 and a secondary magnetic coil 307. The decoupled disturbance signal 10 is applied at the (floating) primary electromagnetic coil 306, resulting in inverted voltage signals at the input points 302 and 304 in relation to a reference point in the middle of the primary electromagnetic coil 306. Then, two mutually inverted signals are applied by the transformer 308 at the ends of the secondary electromagnetic coil 307 due to the resistors 310 and 310′ of the same resistance, which are both connected to the ground. Depending on the switch position, only one of the mutually inverted signals is provided as the intermediate inverted decoupled disturbance signal 12, which corresponds to the decoupled disturbance signal 10 with phase shift 0° or 180°.

(48) A second digital signal switch is provided (signal 0/1) to switch off both operational amplifiers 312 and 314 for deactivating the whole conditioning module (“signal 1”).

(49) FIG. 5 shows a schematic exemplary electrical circuit of the phase shifters 140, 142, which are connected sequentially. A first phase shifter 140, which can be digitally controlled, can be adapted to make coarse phase tuning of an inverted decoupled disturbance signal 12. A second phase shifter 142, which can similarly be digitally controlled, can be adapted to make fine phase tuning of the inverted decoupled disturbance signal 12. They can produce a modified decoupled disturbance signal 14.

(50) Capacitors 404 on the positive input pin of the operational amplifier are selected so that the first shifter 140 can perform a rough shift of 0° . . . 160° in 128 steps (digital 7-bit access), while the second phase shifter 142 can perform a finer resolved shift of 0° . . . 40° in the same number of steps.

(51) At first, the AC signal of the intermediate signal 12 is filtered by only a capacitor 400. The capacitor 400 is necessary when the intermediate signal is on a basic (DC) level, different from the ground level. Such constant signal might be superposed to the decoupled disturbance signal 10 having no influence on the eliminating of the added crosstalk signal.

(52) The phase shift is defined by RC-element 402 with a capacitor 404 and a resistor 406 on the positive input of operational amplifier 408. The resistive part of the RC-element 402 is a digitally controlled resistor 406 (7 bit access), a potentiometer, so that the phase shift can be controlled digitally. Due to the topology of this shifter, the phase shift also affects the amplitude of the signal, which must be accounted for by the next stage 160 shown in FIG. 6. Due to the connection of the resistor 406 to a reference point of a 2.5 V, the output signal of the operational amplifier 408 has an accordingly medium level of 2.5 V.

(53) FIG. 6 shows an exemplary electrical circuit of an amplifier 160, which can be digitally controlled, and can be adapted to adjust the amplitude of a modified decoupled disturbance signal 14 to make it equal to the amplitude of added crosstalk signal incorporated into the measured data signal 20. The amplifier 160 can output a compensation signal 16.

(54) The amplification is performed by a multiplying digital to analog converter 500, where the reference input is the modified decoupled disturbance signal 14.

(55) Upstream of the digital to analog converter (DAC) 500, a capacitor is provided to filter only the AC signal of the modified decoupled disturbance signal 14 filtering the medium level of the signal of 2.5 V.

(56) Different multiplying DACs with different resolution (8 . . . 24 bit access 504) are available. Via this access 504, the amplification provided by digital to analog converter 500 can be controlled. The output signal of the digital to analog converter 500 is then provided to an operational controller 506. The signals accordingly originating from phase shifters and the amplifier device are shown in FIG. 6.

(57) The amplification accounts for the amplitude differences due to different ways of obtaining the added crosstalk signal and the compensation signal as well as for the amplitude loss in the phase shifter stages.

(58) FIG. 7 shows an exemplary electrical circuitry of an adding module 220. It can be adapted to superpose a compensation signal 16 to a measured data signal 20 and it can produce a compensated data signal 22.

(59) If several crosstalk signals are being compensated, they can be added in the same way. The shown topology accounts for four compensation signals 161, 162, 163 and 164 of four different sources of an electromagnetic disturbance, which are at first added up and then provided as one signal to junction 600, to which also the measured data signal 20 is supplied. From the junction 600, the compensated signal 22 is provided to a data-receiving device. In this way, the added crosstalk signals of all four different sources of an electromagnetic disturbance are eliminated.

(60) FIG. 8A shows an embodiment of an extraction device 103 adapted to extract a decoupled disturbance signal 10 from a source of electromagnetic disturbance 100. In the figure, a RF generator 105 is shown which supplies an RF voltage to a load 107 via an electrical circuit. Typically, the load 107 can comprise the electrodes of a quadrupole element in a Fourier transform mass spectrometer, like a quadrupole mass analyser or a quadrupole filter. The RF generator 105 or the load 107, e.g. the electrodes of the quadrupole supplied with the RF voltage may be a source of the electromagnetic disturbance 102. In addition, the RF current in the electrical circuit to supply the voltage to the electrodes can be the source of an electromagnetic disturbance 102. The electromagnetic disturbance 102 is interfering with a measured data signal 20 (not shown here). The extracting device 103 is an additional line 106, which is connected with the circuit supplying the RF voltage and which comprises an impedance component 112a. The extraction device 103 is for example tapping the voltage existing in the electrical circuit supplying the RF voltage to the load 107 at the junction of its additional line 106 with the circuit. The decoupled disturbance signal 10 is then available at the other end of the additional line 106. The impedance component 112a of the additional line 106 can comprise a resistive, an inductive, and/or a capacitive portion. The exact values of the impedance component 112a can depend on the frequencies of the generator 105.

(61) FIG. 8B shows two other embodiments of an extraction device 103 adapted to extract a decoupled disturbance signal 10 from a source of electromagnetic disturbance 100. In the FIG. 8B, a RF generator 105 is also shown, which supplies a RF voltage to a load 107 via an electrical circuit. Typically, the load can comprise the electrodes of a quadrupole element in a Fourier transform mass spectrometer, like a quadrupole mass analyser or a quadrupole filter. Furthermore, the electrical circuit comprises a voltage amplifier 100, which is amplifying the RF voltage provided by the RF generator 105. The RF generator 105 or the load 107, e.g. the electrodes of the quadrupole supplied with the RF voltage may be a source of the electromagnetic disturbance 102. In addition, the RF current in the electrical circuit to supply the voltage to the electrodes can be the source of an electromagnetic disturbance 102. The electromagnetic disturbance 102 is interfering with a measured data signal 20 (not shown here). The extracting device 103 is then an additional line 106, 106′, which is connected with the circuit supplying the RF voltage and which comprises impedance components 112a, 112b. The extraction device 103 is for example tapping the voltage existing in the electrical circuit supplying the RF voltage to the load 107 at the junction of its additional lines 106, 106′ with the circuit. For the additional line 106, the junction is arranged between the RF generator and the voltage amplifier 100. For the additional line 106′, the junction is arranged between the voltage amplifier 100 and the load 107, e.g. the quadrupole electrodes. The decoupled disturbance signal 10 is then available at the other end of the additional lines 106, 106′. The amplitude of the decoupled disturbance signal is different depending on whether the voltage supplied by the RF generator has been amplified before it is tapped by the extraction device 103 or not amplified. The impedance component 112a, 112b of the additional lines 106, 106′ can comprise a resistive, an inductive, and/or a capacitive portion. The exact values of the impedance component 112a, 112b can depend on the frequencies of the generator 105.

(62) FIG. 8C shows further embodiments of extraction devices 103 adapted to extract a decoupled disturbance signal 10 from a source of electromagnetic disturbance 100. In the FIG. 8C, a RF generator 105 is shown, which supplies a load 107 with an RF voltage via a transformer 114. Generally, there is an inductive coupling of the RF generator with the load 107. Typically, the load 107 can comprise the electrodes of a quadrupole element in a Fourier transform mass spectrometer, like a quadrupole mass analyser or a quadrupole filter. Furthermore, the electrical circuit connecting the primary winding of the transformer 114 with the RF generator 105 may comprise a voltage amplifier 100, which can amplify the RF voltage provided by the RF generator 105. The RF generator 105 or the load 107, e.g. the electrodes of the quadrupole supplied with the RF voltage may be a source of the electromagnetic disturbance 102. In addition, the RF current in the electrical circuit to supply the voltage to the primary winding of the transformer 114 or the RF voltage applied at the primary winding of the transformer 114 can be the source of electromagnetic disturbance 102. The electromagnetic disturbance 102 is interfering with a measured data signal 20 (not shown here). The extracting device 103 can then be an additional line 106″ comprising an impedance component 112c which is connected with the electrical circuit supplying the RF voltage from the secondary winding of the transformer 114 to the load 107. The extraction device 103 is able, for example, to tap the voltage existing in the electrical circuit supplying the RF voltage from the secondary winding of the transformer 114 to the load 107 at the junction of the additional line 106″ with the circuit. The decoupled disturbance signal 10 is then available at the other end of the additional line 106″. The impedance component 112c of the additional line 106″ can comprise a resistive, an inductive, and/or a capacitive portion. The exact values of the impedance component 112c can depend on the frequencies of the generator 105. Another embodiment of an extraction device 103 is an antenna 116, which is exposed to the electromagnetic disturbance signal 102. The electromagnetic disturbance signal 102 is inducing a signal in the antenna 116 by crosstalk, which is a decoupled disturbance signal 10 that can be used in the invention. Another embodiment of an extraction device 103 is an additional winding 118, which is inductively coupled with the primary winding of the transformer 114. Then, voltage is induced in additional winding 118, which is then the decoupled disturbance signal 10, which can be used in the invention. The extraction device 103 can output the decoupled disturbance signal 10.

(63) Independently of the configuration or of the schematic position of the extraction device 103, the decoupled disturbance signal 10 follows electromagnetic disturbance signal 102 in form, frequency, and amplitude. Both signals have the same form and frequency. Any change of the form and frequency of the electromagnetic disturbance signal 102 results in the same change of the form and frequency of the decoupled disturbance signal 10. Any relative change of the amplitude of the electromagnetic disturbance signal 102 will result in the same relative change of the amplitude of the decoupled disturbance signal 10. This means that if the amplitude of the electromagnetic disturbance signal 102 changes by an amplification factor Af, wherein Af is the ratio of the amplitude after the change to the amplitude before the change, the amplitude of the decoupled disturbance signal 10 changes also by same amplification factor Af.

(64) FIGS. 9A and 9B depict an exemplary embodiment of mass spectrum, which is the Fourier transform of measured data signal 20, obtained without using the present method of crosstalk signal elimination and with using it, measured by an Orbitrap® mass analyser.

(65) FIG. 9A shows an exemplary signal including a large peak attributed to an electromagnetic disturbance, which is the induced added crosstalk signal. The added crosstalk has frequency of 862.348 kHz, which is adequate to a peak in the mass spectrum of the mass to charge ratio m/z=227.2379.

(66) FIG. 9B depicts a mass spectrum, which is the Fourier transform of an exemplary compensated data signal 22 with no large peak due to the added crosstalk signal eliminated by adding the compensating signal 16 to the measured data signal 20. It can be seen that the noise signal (seen around 860 kHz) has been dramatically reduced, so that it cannot not been observed in the noise of the measurement.

(67) FIGS. 9C, 9D, 9E and 9F depict another exemplary embodiment of mass spectrum of a signal measured by an Orbitrap® mass analyser.

(68) FIGS. 9C and 9D depict the measured data signal 20 in the absence of a sample being measured. In other words, no sample ions are present in the detector for the depicted measurement. FIG. 9C depicts a single peak at 223.206 mass to charge (m/z) ratio. This peak is due to the added crosstalk signal. In FIG. 9D, the same signal is depicted, with the added crosstalk signal compensated by the compensation signal 16.

(69) FIGS. 9E and 9F depict the measured data signal 20 for an exemplary sample comprising inorganic salts (Sodium iodide (NaI): 130 mM, Potassium iodide (KI): 5 mM, and Cesium iodide (CsI): 2 mM). FIG. 9E shows the measured data signal 20 including the added crosstalk signal. Note, that the data peak at 223.205 mass to charge ratio is at about 1.2 relative abundance. FIG. 9F shows the compensated data signal 22 with the added crosstalk signal superposed with the compensation signal 16 in order to substantially eliminate it. The data peak at 223.205 mass to charge ratio is now at about 1.1 relative abundance, which corresponds to the actual value due to the image current induced by the respective ions.

(70) FIGS. 10A, 10B, 10C, and 10D depict an exemplary embodiment of calibrating control parameters of the conditioning module 115 for eliminating the added crosstalk signal.

(71) The exemplarily described here conditioning module 115 comprises the inverter 120, the phase shifters 140 and 142 and the amplitude amplifier 160. These components are digitally controlled and are preferably calibrated at least once for a given disturbance source. These parameters build a four-dimensional search space with for example 2×128×128×1024 variations. A brute force procedure would need too much time to determine an optimal parameter set. The following describes an exemplary schematic calibration procedure that can be used for the determination of the parameter set to eliminate the added crosstalk signal induced by an electromagnetic disturbance 102 of a specific source of an electromagnetic disturbance 100.

(72) The calibration procedure can be applied to a Fourier transform mass spectrometer, e.g. with an Orbitrap® mass analyser.

(73) FIG. 10A shows a first step, which is a rough matching of the amplitudes of the added crosstalk signal 102 and the decoupled disturbance signal 10, when no sample is supplied to the mass analyser of a Fourier transform mass spectrometer. At first, the frequency of the electromagnetic disturbance can be identified in a measured mass spectrum, because this is the only detectable peak in the mass spectrum having the specific frequency of the electromagnetic disturbance 102. During the rough matching, the crosstalk compensation path is first switched off. Then, the amplitude of the disturbance signal 102 in the measured data signal 20 V.sub.dist can be determined. Following this, the crosstalk compensation path can be switched back on, and the signal data path can be switched off. The set parameter of the amplitude amplifier 160 can then be varied so that the amplitude of the compensation signal 16 is matching the amplitude of the measured data signal 20 V.sub.dist. The match is found in FIG. 10A, showing the difference between both signals of the frequency of the detected electromagnetic disturbance 102, when the measured difference is roughly zero. This is also illustrated below as a step-by-step process.

(74) Step 1. Rough Matching of the Amplitudes. a. Switch off the crosstalk compensation path and identify the frequency of the investigated electromagnetic disturbance 102 (see FIG. 9A) b. Determine the amplitude of the added crosstalk signal in the measured data signal 20 V.sub.dist c. Switch on the crosstalk compensation path again and switch off the signal data path (e.g. by switching off the preamplifier 150) d. Vary the set parameter of the amplitude amplifier 160 to match the amplitude of the compensation signal 16 with the determined amplitude of the added crosstalk signal.

(75) In a second step, a sweep through the settings of the phase shifter is made to investigate how the amplitude of the compensation signal 16 is influenced by the phase setting. Only the crosstalk compensation is switched on to condition the decoupled disturbance signal 10 extracted from the source of the electromagnetic disturbance 100. The detector unit 200 is switched off, and no measured data signal 20 is supplied to the adding module 200. First, for this measurement, the amplitude of the compensation signal 16 is set to a high value by a high value amplification by the amplitude amplifier 160. Then, the first phase shifter 140 is set from 0 to 127 consecutively two times, one time without a 180° phase shift by the inverter 120 (“signal 0”) and one time without a 180° phase shift by the inverter 120 (“signal 1”). The change of the amplitude of compensation signal 16, which is the compensated signal 22 due to the switched off detector unit 200, is stored for each setting of the phase shifter. The same sweep is also made for the second phase shifter 142 and, accordingly, the change of the amplitude of compensation signal 16 is stored for each setting of the phase shifter. Based on this change of the amplitude, the amplification setting of the amplifier 160 is adjusted according to the used setting of the phase shifters to compensate the change of the amplitude of the compensation signal 16 with the setting of the phase shifters in the following steps of the calibration.

(76) A Step-by-Step Overview of this Procedure also Follows.

(77) Step 2. Account for Amplitude Influence of the Phase Shifters e. Set amplitude of the compensation signal 16 to a high value f. Set the setting of the first phase shifter 140 from 0 to 127 consecutively and store the change in the amplitude g. Same as f. for phase shifter 142. From this point on, for each setting of phase shifters, the amplitude setting of the amplitude amplifier 160 is adjusted according to the factors measured in f and g.

(78) FIGS. 10B and 10C depict the third step of the calibration procedure, in which a best setting of the phase shifters to condition the decoupled disturbance signal (10) is found. Now, the crosstalk compensation and the detector unit 200 are switched on. For the amplifier 160 the set parameter defined in the first step is now used.

(79) The inverter 120 is then set to 0°. Then the coarse phase shifter 140 is iterated from 0 to 127. Then, the inverter 120 is set to 180°, and the procedure is repeated.

(80) In FIG. 10B, the amplitude of the compensated signal 22 is shown, which is related to the identified frequency of the electromagnetic disturbance 102 for both settings of the inverter 120 and each iteration. The appropriate phase shift can be identified by the minimum of the amplitude of the compensated signal 22, which is given by a 180° phase shift of the inverter 120 and an additional phase shift of roughly 4% by the first phase shifter 140. Following this, both the inverter and the phase shifter are set to these values where the absolute minimum was achieved.

(81) FIG. 10C is showing a fine sweep through the phases to find a minimum represented by darker colours in the colour map. Both phase shifters 140 and 142 are now varied by a few steps around the minimum identified before, and the minimum is determined again.

(82) Step 3. Determine Best Setting for Phase Shifters h. Switch on the signal data path again, and set the amplitude of the compensation signal 16 to the value determined in d. i. Set inverter 120 to 0° and iterate both phase shifters 140 and 142 from 0 to 127 simultaneously. Find the minimum for the disturbing signal in spectrum. j. Same as in i., but with the inverter set to 180°. k. Set the inverter and the shifters to the values where the minimum was found. l. Vary in a range of a few steps both shifters 140 and 142 separately and find the minimum. For example, if the minimum was found at the setting 32, look in the range [16 . . . 48]×[16 . . . 48] for phase shifters 140 and 142 accordingly.

(83) FIG. 10D depicts the fourth step of the calibration procedure comprising a fine matching of the amplitudes of the added crosstalk signal 102 and the decoupled disturbance signal 10 with the newfound matching phases. During this stage, the set parameter of the amplifier 160 is again varied, with the more precise matching phases as found previously in the description to FIG. 10C. In FIG. 10D, the intensity of the compensated signal 22 of the frequency of the investigated electromagnetic disturbance 102 is shown. Because these measurements are performed without a sample, the compensation of the added crosstalk signal induced by the investigated electromagnetic disturbance by the compensation signal 16 due to the set parameter is shown. In this way, the optimised parameters of the amplifier 160 can be identified at the values corresponding to the intensity of the compensated signal 22 being reduced to essentially zero.

(84) Step 4. Fine Matching of the Amplitudes. m. Repeat d. with the best-found setting for the shifters.

(85) In Table 1 below, some of the terms used in the present document are explained, defined and/or exemplified. The given definitions and examples are not exclusive and are given merely for the user's convenience and understanding.

(86) TABLE-US-00001 TABLE 1 Definitions of Terms and Components Source of an e.g. RF power supply of a quadrupole filter, the electrodes of a electromagnetic quadrupole, which is emitting an electromagnetic disturbance 102. disturbance 100 Electromagnetic Emitted signal of a source of electromagnetic disturbance 100 disturbance 102 influencing the measured data signal 20 of a detector unit 200, in particular of a Fourier transform mass spectrometer. Detector unit Unit, in particular of a Fourier transform mass spectrometer, 200 measuring a data signal, generated by an image current, in particular induced by ions in a mass analyser, whereby the unit may comprise further components like a preamplifier to change the image current into a measured data signal. Measured data Signal measured by the detector unit 200 provided by an interface signal 20 to the periphery. Undisturbed Signal measured by the detector unit 200 provided by an interface measured data to the periphery, when no source of an electromagnetic disturbance signal 18 is influencing the measured data signal 20. Crosstalk Interaction, in particular interference, between an electromagnetic disturbance and a detector unit modifying the measured data signal in comparison to the undisturbed measured data signal. In particular, it can be a superposition of at least a part of the electromagnetic disturbance with the undisturbed measured data signal. Added crosstalk Signal added to the undisturbed measured data signal by the signal crosstalk of an electromagnetic disturbance and the detector unit resulting in the measured data signal. undisturbed data measured data + added crosstalk signal = measured data signal Extraction Device which extracts a signal from a source of an electromagnetic device 103 disturbance, the decoupled disturbance signal 10, which is correlated to the electromagnetic disturbance having the same shape and frequency and being correlated to the amplitude of the electromagnetic disturbance. Decoupled Signal extracted by an extraction device 103 from a source of an disturbance electromagnetic disturbance which is correlated to the signal 10 electromagnetic disturbance 102 having the same shape and frequency and being correlated to the amplitude of the electromagnetic disturbance. Conditioning Module, to which a decoupled disturbance signal 10 is provided. module 115 The conditioning module 115 is conditioning the decoupled disturbance signal 10 to obtain the compensation signal 16 by applying only a phase shift and/or an amplitude amplification to the decoupled disturbance signal 10. Preferably, the condition module comprises both components: phase shifter 170 and amplification module 160. Phase shifter The phase shifter has two functions. It inverts the decoupled 170 disturbance signal 10 and compensates any phase difference Δφ, which the compensation signal 16 and the measured data signal 20 would have at the adding module 220, which is different from 180°, by an additional phase shift −Δφ. In general, an essential phase inversion of the compensation signal is sufficient to eliminate the added crosstalk signals according to the invention. φ.sub.ms phase angle of the measured data signal 20 at the adding module 220 φ.sub.cs phase angle of the compensation signal 16 superposed to the measured data signal 20 at the adding module 220 φ.sub.cs − φ.sub.ms =180° φ.sub.inv phase angle of the compensation signal 16 at the adding module 220 without additional phase shift, if only a phase shift of 180° is applied to the decoupled disturbance signal 10 φ.sub.inv − φ.sub.ms =180° + Δφ Amplification The amplifier 160 modifies the amplitude of the decoupled module 160 disturbance signal as part of the conditioning module 115, so that the amplitude of the decouple disturbance signal matches the amplitude of the compensation signal 16. Compensation The compensation signal 16 is provided by the conditioning signal 16 module 115 when a decoupled disturbance signal 10 is provided to the conditioning module 115. Adding module The measured data signal 20 and the compensation signal 16 are 220 provided to the adding module 220, preferably at one junction 600. Both signals are superposed to obtain the compensated data signal 22 by the adding module, which is essentially the same signal, which would be provided by the detector unit 200 without any interference from the source of electromagnetic disturbance 100. Compensated The compensated signal 22 is provided by the adding module 220 signal 22 and is essentially the same signal, which would be provided by the detector unit 200 without any source of electromagnetic disturbance 100.

(87) As used herein, including in the claims, singular forms of terms are to be construed as also including the plural form and vice versa, unless the context indicates otherwise. Thus, it should be noted that as used herein, the singular forms “a,” “an,” and “the” include plural references unless the context clearly dictates otherwise.

(88) Throughout the description and claims, the terms “comprise”, “including”, “having”, and “contain” and their variations should be understood as meaning “including but not limited to”, and are not intended to exclude other components if not in detail stated in the description.

(89) The term “at least one” should be understood as meaning “one or more”, and therefore includes both embodiments that include one or multiple components. Furthermore, dependent claims that refer to independent claims that describe features with “at least one” have the same meaning, both when the feature is referred to as “the” and “the at least one”.

(90) It will be appreciated that variations to the foregoing embodiments of the invention can be made while still falling within the scope of the invention can be made while still falling within scope of the invention. Features disclosed in the specification, unless stated otherwise, can be replaced by alternative features serving the same, equivalent or similar purpose. Thus, unless stated otherwise, each feature disclosed represents one example of a generic series of equivalent or similar features.

(91) Use of exemplary language, such as “for instance”, “such as”, “for example” and the like, is merely intended to better illustrate the invention and does not indicate a limitation on the scope of the invention unless so claimed. Any steps described in the specification may be performed in any order or simultaneously, unless the context clearly indicates otherwise.

(92) All of the features and/or steps disclosed in the specification can be combined in any combination, except for combinations where at least some of the features and/or steps are mutually exclusive. In particular, preferred features of the invention are applicable to all aspects of the invention and may be used in any combination.