CONTINUOUSLY ADJUSTABLE ANALOG PHASE SHIFTER

Abstract

The invention discloses a continuously adjustable analog phase shifter, comprising N series-connected lumped phase shift units, with N≥1, where the ith lumped phase shift unit is a high-pass lumped phase shift unit or a low-pass lumped phase shift unit, with 1≤i≤N. The invention adopts a lumped phase shift unit, and utilizes the advantage of small size of the lumped parametric circuit, thereby allowing the phase shifter to have a compact structure, small area, low cost and convenient integration. The lumped phase shift units in the invention may be selected as all high-pass lumped phase shift units or low-pass lumped phase shift units as appropriate, thereby having a flexible circuit structure that can meet the requirements at various operation frequencies. The lumped phase shift units in the invention may be selected to take the form of series-connected high-pass lumped phase shift unit and low-pass lumped phase shift unit, thereby permitting a wider bandwidth.

Claims

1. A continuously adjustable analog phase shifter, comprising N series-connected lumped phase shift units, with N≥1, where the ith lumped phase shift unit is a high-pass lumped phase shift unit or a low-pass lumped phase shift unit, with 1≤i≤N.

2. The continuously adjustable analog phase shifter of claim 1, wherein the high-pass lumped phase shift unit comprises a first inductor L1, one end of the first inductor L1 being connected to the anode of a first voltage-controlled varactor diode D1, the cathode of the first voltage-controlled varactor diode D1 being connected respectively to one end of the second inductor L2 and the anode of a second voltage-controlled varactor diode D2, the other end of the second inductor L2 being grounded, the cathode of the second voltage-controlled varactor diode D2 being connected to the other end of the first inductor L1; where one end of the first inductor L1 serves as the input of the high-pass lumped phase shift unit and the other end of the first inductor L1 serves as the output of the high-pass lumped phase shift unit.

3. The continuously adjustable analog phase shifter of claim 2, wherein the first inductor L1 and the second inductor L2 are both spiral inductors.

4. The continuously adjustable analog phase shifter of claim 2, wherein the first inductor L1 has an inductance of 2R/ω.sub.0 and the second inductor L2 has an inductance of R/ω.sub.0, and the first voltage-controlled varactor diode D1 and the second voltage-controlled varactor diode D2 both have a capacitance of 1/Rω.sub.0, where R is the input impedance of the phase shifter and ω.sub.0 is the center frequency of the high-pass lumped phase shift unit.

5. The continuously adjustable analog phase shifter of claim 1, wherein the low-pass lumped phase shift unit comprises a third inductor L3, one end of the third inductor L3 being connected to the anode of the third voltage-controlled varactor diode D3, and the other end of the third inductor L3 being connected respectively to one end of the fourth inductor L4 and the cathode of the fourth voltage-controlled varactor diode D4, the anode of the fourth voltage-controlled varactor diode D4 being grounded, and the other end of the fourth inductor L4 being connected to the cathode of the third voltage-controlled varactor diode D3, where one end of the third inductor L3 serves as the input of the low-pass lumped phase shift unit, and the other end of the fourth inductor L4 serves as the output of the low-pass lumped phase shift unit.

6. The continuously adjustable analog phase shifter of claim 5, wherein the third inductor L3 and the fourth inductor L4 are both spiral inductors.

7. The continuously adjustable analog phase shifter of claim 5, wherein the third inductor L3 and the fourth inductor L4 both have an inductance of R/ω.sub.1, the third voltage-controlled varactor diode D3 has a capacitance of ½Rω.sub.1 and the fourth voltage-controlled varactor diode D4 has a capacitance of 2/Rω.sub.1, where R is the input impedance of the phase shifter and ω.sub.1 is the center frequency of the low-pass lumped phase shift unit.

Description

BRIEF DESCRIPTION OF THE DRAWINGS

[0017] FIG. 1 (a) is a schematic view of a phase shifter enabling 180° phase shifting in prior art;

[0018] FIG. 1 (b) is a schematic view of a reflective circuit in prior art;

[0019] FIG. 1 (c) is a schematic view of a phase shifter enabling 360° phase shifting in prior art;

[0020] FIG. 2 is a schematic view of a phase shifter according to a particular embodiment of the invention;

[0021] FIG. 3 is a schematic view of a low-pass lumped phase shift unit according to a particular embodiment of the invention;

[0022] FIG. 4 is a schematic view of a high-pass lumped phase shift unit according to a particular embodiment of the invention;

[0023] FIGS. 5 (a) to 5 (c) are a diagram showing the simulation results of a phase shifter according to a particular embodiment of the invention;

[0024] FIG. 5 (a) is a diagram showing the simulation results of the input/output return loss of an analog phase shifter with 6-12 GHz 360-degree continuously adjustable phase;

[0025] FIG. 5 (b) is a diagram showing the simulation results of the insertion loss in various phase shift statuses of an analog phase shifter with 6-12 GHz 360-degree continuously adjustable phase; and

[0026] FIG. 5 (c) is a diagram showing the simulation results of the phase shift range of an analog phase shifter with 6-12 GHz 360-degree continuously adjustable phase at a control voltage of 0 to 10V.

DETAILED DESCRIPTION

[0027] The phase shifter enabling 180° phase shafting in prior art, as shown in FIG. 1 (a), includes a 3 dB coupler with a varactor diode loaded at its terminal and a reflective circuit. The reflective circuit, as shown in FIG. 1 (b), includes a fifth inductor L5. One end of the fifth inductor L5 is connected to one end of a first variable capacitor C1. The other end of the first variable capacitor C1 is grounded. The other end of the fifth inductor L5 is connected to one end of the second variable capacitor C2. The other end of the second variable capacitor C2 is grounded. The phase shifter enabling 360° phase shafting in prior art, as shown in FIG. 1 (c), is formed by two 180° phase shifters that are connected in series. However, the 3 dB coupler has the disadvantages of large area, inconvenient integration, and increased circuit cost. The traditional reflective circuit can hardly meet the requirements of broadband and miniaturization.

[0028] To overcome the disadvantages of prior art, this particular embodiment discloses a continuously adjustable analog phase shifter which, as shown in FIG. 2, includes N series-connected lumped phase shift units, with N≥1, among which the ith lumped phase shift unit is a high-pass lumped phase shift unit or a low-pass lumped phase shift unit, with 1≤i≤N.

[0029] As shown in FIG. 4, the high-pass lumped phase shift unit includes a first inductor L1. One end of the first inductor L1 is connected to the anode of the first voltage-controlled varactor diode D1. The cathode of the first voltage-controlled varactor diode D1 is connected respectively to one end of the second inductor L2 and the anode of the second voltage-controlled varactor diode D2. The other end of the second inductor L2 is grounded. The cathode of the second voltage-controlled varactor diode D2 is connected to the other end of the first inductor L1. One end of the first inductor L1 serves as the input of the high-pass lumped phase shift unit, and the other end of the first inductor L1 serves as the output of the high-pass lumped phase shift unit.

[0030] The first inductor L1 has an inductance of 2R/ω.sub.0 and the second inductor L2 has an inductance of R/ω.sub.0, and the first voltage-controlled varactor diode D1 and the second voltage-controlled varactor diode D2 both have a capacitance of 1/Rω.sub.0, where R is the input impedance of the phase shifter and coo is the center frequency of the high-pass lumped phase shift unit. The input impedance of the phase shifter is equal to the output impedance, typically 50 Ohm.

[0031] As shown in FIG. 3, the low-pass lumped phase shift unit includes a third inductor L3. One end of the third inductor L3 is connected to the anode of the third voltage-controlled varactor diode D3. The other end of the third inductor L3 is connected respectively to one end of the fourth inductor L4 and the cathode of the fourth voltage-controlled varactor diode D4. The anode of the fourth voltage-controlled varactor diode D4 is grounded. The other end of the fourth inductor L4 is connected to the cathode of the third voltage-controlled varactor diode D3. One end of the third inductor L3 serves as the input of the low-pass lumped phase shift unit and the other end of the fourth inductor L4 serves as the output of the low-pass lumped phase shift unit.

[0032] The third inductor L3 and the fourth inductor L4 both have an inductance of R/ω.sub.1, the third voltage-controlled varactor diode D3 has a capacitance of ½Rω.sub.1 and the fourth voltage-controlled varactor diode D4 has a capacitance of 2/Rω.sub.1, where R is the input impedance of the phase shifter and ω.sub.1 is the center frequency of the low-pass lumped phase shift unit.

[0033] The phase response θ(ω) of a single low-pass lumped phase shift unit is expressed in the equation (2), where is expressed in the equation (3).

[00001]$\begin{array}{cc}\theta \left(\omega \right)=2{\tan }^{-1}\left(\frac{{\mathrm{\omega \omega }}_c}{{\omega }^2-{\omega }_c^2}\right)& \left(2\right)\\ {\omega }_c=\omega \text{?}\sqrt{\frac{C_{n,i}}{C_i}}\text{?}\text{indicates text missing or illegible when filed}& \left(3\right)\end{array}$

[0034] In the equation (3), is the initial capacitance of the ith voltage-controlled varactor diode at a control voltage of 0V, with 1=3 or 4. When 1=3, C.sub.n,3 is the initial capacitance of the third voltage-controlled varactor diode D3 at a control voltage of 0V. When i=4, C.sub.n,4 is the initial capacitance of the fourth voltage-controlled varactor diode D4 at a control voltage of 0V. C.sub.i is the maximum capacitance of the ith voltage-controlled varactor diode. When 1=3, C.sub.3 is the maximum capacitance of the third voltage-controlled varactor diode D3. When 1=4, C.sub.4 is the maximum capacitance of the fourth voltage-controlled varactor diode D4. ω.sub.c is the resonant frequency at the time when the capacitance of the third voltage-controlled varactor diode D3 changes from C.sub.n,3 to C.sub.3 as the control voltage changes, and is also the resonant frequency at the time when the capacitance of the fourth voltage-controlled varactor diode D4 changes from C.sub.n,4 to C.sub.4 as the control voltage changes. For a single low-pass lumped phase shift unit, the maximum phase shift occurs in the maximum range of capacitance change, i.e., C.sub.min to C.sub.max. Therefore, the size of the third voltage-controlled varactor diode D3 and the fourth voltage-controlled varactor diode D4 can be selected based on the desired phase shift range and the return loss.

[0035] In the field of phased arrays, all-band 360° accumulative phase shifting is typically desired. Therefore, a series connection of multi-stage lumped phase shift units is often desired. By the series connection of lumped phase shift units of different center frequencies, not only is phase shift increased, but also wide bandwidth and flat phase shift response are enabled. For example, in a phase shifter with four low-pass lumped phase shift units, two of which are low-pass lumped phase shift units of a center frequency of 6 GHz and the other two of which are low-pass lumped phase shift units of a center frequency of 12 GHz, the initial values of various lumped phase shift units in the analog phase shifter with 6-12 GHz all-band 360° continuously adjustable phase can be determined and locally optimized to achieve the aim. FIGS. 5 (a) to 5 (c) are diagrams showing the simulation results of an analog phase shifter with 6-12 GHz all-band 360° continuously adjustable phase. As shown in FIG. 5 (a), the return loss of the phase shifter has a typical value of −13 dB, which represents a desirable return characteristic. As shown in FIG. 5 (b), the insertion loss of the phase shifter has a typical value of −4 dB, which is very low and represents a desirable linearity. As shown in FIG. 5 (c), the phase shifter enables a phase shift range greater than 360 degrees over 6-12 GHz all band with little phase shift fluctuation.