LINEARIZATION WITH LEVEL TRACKING

Abstract

Disclosed are systems, devices, modules, methods, and other implementations, including a method for digital predistortion that includes receiving, by a digital predistorter, a first signal that depends on amplitude variations based on an input signal, u, with the variations of the first signal corresponding to time variations in non-linear characteristics of a transmit chain that includes a power amplifier. The method further includes receiving, by the digital predistorter, the input signal u, generating, by the digital predistorter, based at least in part on signals comprising the input signal u and the first signal, a digitally predistorted signal v to mitigate the non-linear behavior of the transmit chain, and providing the predistorted signal v to the transmit chain.

Claims

1.-48. (canceled)

49. A method comprising: receiving, by a power supply modulator, one or more control signals; and regulating, based on the one or more control signals, power supply provided to a power amplifier of a transmit chain to underpower the power amplifier so that the transmit chain includes at least some non-linear behavior; wherein the at least some non-linear behavior of the transmit chain, resulting from regulating the power supply based on the one or more control signals, is at least partly mitigated through digital predistortion performed by a digital predistorter on signals comprising an input signal, u, provided to the digital predistorter, and on another signal, provided to the digital predistorter, that depends on amplitude variations based on the input signal, u, wherein the variations of the other signal correspond to time variations in non-linear characteristics of the transmit chain.

50. The method of claim 49, wherein the other signal provided to the digital predistorter includes a time-varying signal e generated by an envelope tracker that receives a copy of the input signal u.

51. The method of claim 50, wherein the time-varying control signal e is derived based on a set of constraints, including: a first constraint in which e[t]≥h(|u[t]|), where h(⋅) defines a relation between instantaneous power of the input signal u and a power supply of the transmit chain, a second constraint imposing maximal value and curvature bounds for the signal e, such that
e[t]≤E0, and |2e[t]−e[t−1]−e[t+1]|≤E2, where E0 and E2 are values representative of operational characteristics of the power amplifier, and a third constraint requiring that values of e[t] be as small as possible, subject to the first and second constraints.

52. The method of claim 51, wherein E2 is representative of one or more of: a bandwidth of the transmit chain, or a response speed of the transmit chain to variations in amplitude of the input signal u.

53. (canceled)

54. The method of claim 50, wherein receiving the one or more control signals comprises: receiving a time-varying signal, e.sub.A, generated through digital predistortion performed on multiple signals comprising the input signal u and the time-varying signal e, to mitigate non-linear behavior of the power supply modulator producing output based on the resultant time-varying signal, e.sub.A.

55. The method of claim 54, wherein the digital predistorter is configured to generate digitally predistorted output signal, v, from the multiple signals comprising the input signal u and the time-varying control signal e, according to: $v\left[t\right]=u\left[t\right]+\underset{k=1}{\overset{n}{.Math.}}.Math.x_k.Math.B_k\left(q_u\left[t\right],q_e\left[t\right]\right)$ $\mathrm{with}$ $q_u\left[t\right]=\left[\begin{array}{c}u\left[t+l-1\right]\\ u\left[t+l-2\right]\\ \mathrm{.Math.}\\ u\left[t+l-\tau \right]\end{array}\right]$ $\mathrm{and}.Math..Math.\mathrm{with}$ $q_e\left[t\right]=\left[\begin{array}{c}e\left[t+s\left(l-1\right)\right]\\ e\left[t+s\left(l-2\right)\right]\\ \mathrm{.Math.}\\ e\left[t+s\left(l-\tau \right)\right]\end{array}\right]$ wherein B.sub.k are basis functions, q.sub.u[t] and q.sub.e[t] are stacks of recent baseband and envelope input samples, respectively, s is a time scale separation factor representative of a ratio of time constants of the power amplifier and the power supply modulator powering the power amplifier, and x.sub.k are computed coefficients to weigh the basis functions.

56. The method of claim 55, wherein the coefficients x.sub.k are computed according to an optimization process based, at least in part, on observed samples of the transmit chain.

57. The method of claim 56, wherein the coefficients x.sub.k computed according to the optimization process are computed according to the optimization process and further based on an output of the power supply modulator, the output being one of: a voltage provided to the power amplifier, or a control signal to cause a corresponding voltage to be provided to the power amplifier.

58. The method of claim 53, wherein receiving the time-varying signal e.sub.A comprises: receiving the time-varying control signal, e.sub.A, generated as a bandwidth lowering function of the time-varying signal e.

59. The method of claim 49, wherein the other signal provided to the digital predistorter includes an observed digital sample, y, of an output of the power amplifier, the power amplifier being controlled by the power supply modulator according to a time-varying signal e generated by an envelope tracker that receives a copy of the input signal u.

60. The method of claim 49, wherein the other signal provided to the digital predistorter includes a predicted signal, s.sub.p, computed by a predictor module electrically interposed between an envelope tracker and the digital predistorter, the predicted signal being representative of an estimated expected behavior of the power supply modulator based on known characteristics of the power supply module and a time-varying signal, e, determined by the envelope tracker.

61. A power supply modulator to control electrical operation of a transmit chain, the power supply modulator comprising: a receiver to receive one or more control signals; and a regulator to regulate, based on the one or more control signals, power supply provided to a power amplifier of the transmit chain to underpower the power amplifier so that the transmit chain includes at least some non-linear behavior; wherein the at least some non-linear behavior of the transmit chain, resulting from regulating the power supply based on the one or more control signals, is at least partly mitigated through digital predistortion performed by a digital predistorter on signals comprising an input signal, u, provided to the digital predistorter, and on another signal, provided to the digital predistorter, that depends on amplitude variations based on the input signal, u, wherein the variations of the other signal correspond to time variations in non-linear characteristics of the transmit chain.

62. The power supply modulator of claim 61, wherein the other signal provided to the digital predistorter includes a time-varying signal e generated by an envelope tracker that receives a copy of the input signal u.

63. The power supply modulator of claim 62, wherein the time-varying control signal e is derived based on a set of constraints, including: a first constraint in which e[t]≥h(|u[t]|), where h(⋅) defines a relation between instantaneous power of the input signal u and a power supply of the transmit chain, a second constraint imposing maximal value and curvature bounds for the signal e, such that
e[t]≤E0, and |2e[t]−e[t−1]−e[t+1]|≤E2, where E0 and E2 are values representative of operational characteristics of the power amplifier, and a third constraint requiring that values of e[t] be as small as possible, subject to the first and second constraints.

64.-65. (canceled)

66. The power supply modulator of claim 62, wherein the receiver configured to receive the one or more control signals is configured to: receive a time-varying signal, e.sub.A, generated through digital predistortion performed on multiple signals comprising the input signal u and the time-varying signal e, to mitigate non-linear behavior of the power supply modulator producing output based on the resultant time-varying signal, e.sub.A.

67.-72. (canceled)

73. A method for digital predistortion comprising: receiving an input signal, u; determining, by an envelope tracking module, based on amplitude variations of the input signal u, a time-varying signal, e; causing a power supply modulator controlling electrical operation of a transmit chain to underpower a power amplifier of the transmit chain using the time-varying signal e so as to cause the transmit chain to operate in a non-linear mode; predistorting the input signal, u, by a digital predistorter, to yield a digitally predistorted output, v, to mitigate non-linear operation of the transmit chain in the non-linear mode caused by underpowering of the power amplifier; and providing the digitally predistorted output, v, to the transmit chain for processing via the power amplifier.

74. The method of claim 73, wherein determining the time-varying signal, e, comprises: deriving the time-varying signal, e, according to one or more constraints representative of characteristics of the transmit chain.

75. The method of claim 74, wherein deriving the time-varying signal e comprises: deriving the time-varying signal e satisfying a set of constraints that includes: a first constraint in which e[t]≥h(|u[t]|), where h(⋅) defines a relation between instantaneous power of the input signal u and a power supply of the transmit chain, a second constraint imposing maximal value and curvature bounds for the signal e, such that
e[t]≤E0, and |2e[t]−e[t−1]−e[t+1]|≤E2, where E0 and E2 are values representative of operational characteristics of the power amplifier, and a third constraint requiring that values of e[t] be as small as possible, subject to the first and second constraints.

76. The method of claim 75, wherein E2 is representative of one or more of: a bandwidth of the transmit chain, or a response speed of the transmit chain to variations in amplitude of the input signal u.

77. The method of claim 73, further comprising: providing, by the envelope tracking module, the time-varying signal e to the digital predistorter, wherein the digital predistorter processes the input signal, u, and the time-varying signal, e, to yield the digitally predistorted output, v.

78. The method of claim 77, wherein providing the time-varying signal to the digital predistorter comprises: providing the time-varying signal e to the digital predistorter to generate through digital predistortion performed on the input signal u and on the time-varying signal e, a resultant control signal, e.sub.A, provided to the power supply modulator controlling the electrical operation of the transit chain.

79. The method of claim 78, wherein the digital predistorter configured to produce the resultant control signal e.sub.A is configured to: compute, based, at least in part, on observed samples of the transmit chain, coefficients to weigh basis functions applied to samples of the input signal u and the time-varying signal e to generate the resultant control signal e.sub.A.

80. The method of claim 73, further comprising: providing the time-varying signal e to the power supply modulator controlling electrical operation of the transmit chain, wherein the digital predistorter receives an observed digital sample, y, of an output of the power amplifier.

81. The method of claim 80, further comprising: providing the time-varying signal e to a predictor module electrically interposed between the envelope tracking module and digital predistorter, the predictor module configured to compute a predicted signal, s.sub.p, representative of an estimated expected behavior of a power supply modulator, controlling electrical operation of the transmit chain, based on known characteristics of the power supply module and the determined time-varying signal e, wherein the other input signal of the digital predistorter includes the predicted signal, s.sub.p, computed by the predictor module.

82. The method of claim 73, wherein the digital predistorter configured to generate the digitally predistorted output, v, is configured to: generate the digitally predistorted output, v, based on the input signal u and the time-varying signal, e, according to: $v\left[t\right]=u\left[t\right]+\underset{k=1}{\overset{n}{.Math.}}.Math.x_k.Math.B_k\left(q_u\left[t\right],q_e\left[t\right]\right)$ $\mathrm{with}$ $q_u\left[t\right]=\left[\begin{array}{c}u\left[t+l-1\right]\\ u\left[t+l-2\right]\\ \mathrm{.Math.}\\ u\left[t+l-\tau \right]\end{array}\right]$ $\mathrm{and}.Math..Math.\mathrm{with}$ $q_e\left[t\right]=\left[\begin{array}{c}e\left[t+s\left(l-1\right)\right]\\ e\left[t+s\left(l-2\right)\right]\\ \mathrm{.Math.}\\ e\left[t+s\left(l-\tau \right)\right]\end{array}\right]$ wherein B.sub.k are basis functions, q.sub.u[t] and q.sub.e[t] are stacks of recent baseband and envelope input samples, respectively, s is a time scale separation factor representative of a ratio of time constants of the power amplifier and the power supply modulator powering the power amplifier, and x.sub.k are computed coefficients to weigh the basis functions.

83. An envelope tracking module comprising: a receiver to receive an input signal u, the input signal u further provided to a digital predistorter coupled to a transmit chain comprising a power amplifier; a controller to determine, based on amplitude variations of the input signal u, a time-varying signal, e, wherein the amplitude variations of the time-varying signal e correspond to time variations in non-linear characteristics of the transmit chain, wherein the controller configured to determine the time-varying signal, e, is configured to determine the time-varying signal e to cause a power supply modulator controlling the electrical operation of the transit chain to underpower the power amplifier so as to cause the transmit chain to operate in a non-linear mode; and an output section to output the time-varying signal e; wherein the digital predistorter is configured to receive another input signal that depends on the amplitude variations of the time-varying signal e, and to generate, based at least in part on signals comprising the input signal u and the other input signal, a digitally predistorted output, v, provided to the transmit chain, to mitigate non-linear behavior of the transmit chain.

84. The envelope tracking module of 83, wherein the controller configured to determine the time-varying signal, e, is configured to: derive the time-varying signal, e, according to one or more constraints representative of characteristics of the transmit chain, the constraints including: a first constraint in which e[t]≥h(|u[t]|), where h(⋅) defines a relation between instantaneous power of the input signal u and a power supply of the transmit chain, a second constraint imposing maximal value and curvature bounds for the signal e, such that
e[t]≤E0, and |2e[t]−e[t−1]−e[t+1]|≤E2, where E0 and E2 are values representative of operational characteristics of the power amplifier, and a third constraint requiring that values of e[t] be as small as possible, subject to the first and second constraints.

85. The envelope tracking module of claim 83, wherein the output section is further configured to perform one of: provide the time-varying signal e to the digital predistorter, wherein the other input signal of the digital predistorter includes the time varying signal e; or provide the time-varying signal e to the power supply modulator controlling electrical operation of the transmit chain, wherein the other input signal of the digital predistorter includes an observed digital sample, y, of an output of the power amplifier.

86. The envelope tracking module of claim 83, wherein the output section is further configured to: provide the time-varying signal e to a predictor module electrically interposed between the envelope tracking module and digital predistorter, the predictor module configured to compute a predicted signal, s.sub.p, representative of an estimated expected behavior of a power supply modulator, controlling electrical operation of the transmit chain, based on known characteristics of the power supply module and the determined time-varying signal e, wherein the other input signal of the digital predistorter includes the predicted signal, s.sub.p, computed by the predictor module.

87. The envelope tracking module of claim 83, wherein the digital predistorter configured to generate the digitally predistorted output, v, is configured to: generate the digitally predistorted output, v, based on the input signal u and the time-varying signal, e, according to: $v\left[t\right]=u\left[t\right]+\underset{k=1}{\overset{n}{.Math.}}.Math.x_k.Math.B_k\left(q_u\left[t\right],q_e\left[t\right]\right)$ $\mathrm{with}$ $q_u\left[t\right]=\left[\begin{array}{c}u\left[t+l-1\right]\\ u\left[t+l-2\right]\\ \mathrm{.Math.}\\ u\left[t+l-\tau \right]\end{array}\right]$ $\mathrm{and}.Math..Math.\mathrm{with}$ $q_e\left[t\right]=\left[\begin{array}{c}e\left[t+s\left(l-1\right)\right]\\ e\left[t+s\left(l-2\right)\right]\\ \mathrm{.Math.}\\ e\left[t+s\left(l-\tau \right)\right]\end{array}\right]$ wherein B.sub.k are basis functions, q.sub.u[t] and q.sub.e[t] are stacks of recent baseband and envelope input samples, respectively, s is a time scale separation factor representative of a ratio of time constants of the power amplifier and the power supply modulator powering the power amplifier, and x.sub.k are computed coefficients to weigh the basis functions.

88. The envelope tracking module of claim 83, wherein the output section is further configured to: provide the time-varying signal e to the digital predistorter to generate through digital predistortion performed on the input signal u and on the time-varying signal e, a resultant control signal, e.sub.A, provided to a power supply modulator controlling the electrical operation of the transit chain.

Description

BRIEF DESCRIPTION OF DRAWINGS

[0059] These and other aspects will now be described in detail with reference to the following drawings.

[0060] FIG. 1 is a diagram of a linearization system implementation.

[0061] FIG. 2 is a diagram of an actuator, with an example inputs/output configuration.

[0062] FIG. 3 is a block diagram of an adjustable pre-distorting power amplifier system which may be used, at least in part, in implementations of the system of FIG. 1.

[0063] FIG. 4 is a flowchart of an example procedure for digital predistortion.

[0064] FIG. 5 is a flowchart of an example procedure to control electrical operation of a transmit chain.

[0065] FIGS. 6A-C are graphs showing different envelope tracking responses.

[0066] FIG. 7 is a flowchart of an example procedure, generally performed at a power supply modulator, to control electrical operation of a transmit chain.

[0067] FIG. 8 is a diagram of another example linearization system.

[0068] FIG. 9 is a diagram of another example implementation of a linearization system that includes a predictor module electrically interposed between an output of an envelope generator and a digital predistorter.

[0069] Like reference symbols in the various drawings indicate like elements.

DETAILED DESCRIPTION

[0070] Described are various digital predistortion implementations that include an envelope generator that can generate a slow or fast envelope signal (depending on available bandwidth), an actuator (predistortion) block that depends on both the signal itself and the envelope to thus use the envelope signal e (in addition to u) to generate the pre-distorted output v provided to the transmit chain. The system is able to generate an optimal shaping table for a given PA set-up and performance targets. The envelope generator implements an advanced function to convert an input signal (e.g., baseband input), u, into a safe (e.g., from a power consumption perspective) and efficient envelope signal, e. The actuator block is configured to also generate a resultant envelope signal, e.sub.A, that can be optimized to generate better linearization results with a bandwidth that is compatible with a power supply modulator of the linearization system.

[0071] Thus, in some embodiments, an example method for digital predistortion, generally performed at a digital predistorter of a linearization system, is provided. The method includes receiving (by a digital predistorter) a first signal that depends on amplitude variations based on an input signal, u, with the variations of the first signal corresponding to time variations in non-linear characteristics of a transmit chain that includes a power amplifier. The method further includes receiving (by the digital predistorter) the input signal u, generating, by the digital predistorter, based at least in part on signals comprising the input signal u and the first signal, a digitally predistorted signal v to mitigate the non-linear behavior of the transmit chain, and providing the predistorted signal v to the transmit chain. In some embodiments, the first signal may be the output of an envelope tracker, in which case receiving the first signal may include monitoring by the digital predistorter a time-varying signal e generated by an envelope tracker (the envelope tracking module which may be a separate module from the digital predistorter) that received a copy of the input signal u. In some examples, the time-varying signal e is generated from the input signal u such that the time-varying signal e causes at least some non-linear behavior of the power amplifier. In such examples, generating the digitally predistorted signal v may include using the time-varying signal e to digitally predistort the input signal u such that the output of the transmit chain resulting from digitally predistorting the input signal u is substantially free of the at least some non-linear distortion caused by the time-varying signal e.

[0072] In additional implementations described herein, an example method to control electrical operation of a transmit chain, generally performed by an envelope tracking module of a linearization system, is provided. The method includes receiving by an envelope tracking module an input signal u, with the input signal u further provided to a digital predistorter coupled to a transmit chain that includes a power amplifier. The method further includes determining, by the envelope tracking module, based on amplitude variations of the input signal u, a time-varying signal, e, with the amplitude variations of the time-varying signal e correspond to time variations in non-linear characteristics of the transmit chain, and outputting, by the envelope tracking module, the time-varying signal e. The digital predistorter is configured to receive another input signal that depends on the amplitude variations of the time-varying signal e, and to generate, based at least in part on signals comprising the input signal u and the other input signal, a digitally predistorted output, v, provided to the transmit chain, to mitigate non-linear behavior of the transmit chain. In some embodiments, the other input signal provided to the digital predistorter is the time varying signal e determined by the envelope tracking module. The digital predistorter is further configured, in such embodiments, to additionally produce a resultant control signal, e.sub.A, provided to a power supply modulator controlling the electrical operation of the transit chain.

[0073] In further implementations described herein, an example method to control electrical operation of a transmit chain, generally performed at a power supply modulator of a linearization system, is provided. The method includes receiving, by a power supply modulator, one or more control signals, and regulating, based on the one or more control signals, power supply provided to a power amplifier of a transmit chain to underpower the power amplifier so that the transmit chain includes at least some non-linear behavior. The at least some non-linear behavior of the transmit chain, resulting from regulating the power supply based on the one or more control signals, is at least partly mitigated through digital predistortion performed by a digital predistorter on signals comprising an input signal, u, provided to the digital predistorter, and on another signal, provided to the digital predistorter, that depends on amplitude variations based on an input signal, u, wherein the variations of the other signal correspond to time variations in non-linear characteristics of the transmit chain. In some embodiments, the other signal provided to the digital predistorter includes a time-varying signal e generated by an envelope tracker that receives a copy of the input signal u. In some examples, the time-varying signal e is derived based on a set of constraints that includes a first constraint in which e[t]≥h(|u[t]|), where h(⋅) defines a relation between instantaneous power of the input signal u and a power supply of the transmit chain, a second constraint imposing maximal value and curvature bounds for the signal e, such that e[t]≤E0, and |2e[t]−e[t−1]−e[t+1]|≤E2, where E0 and E2 are values representative of operational characteristics of the power amplifier, and a third constraint requiring that values of e[t] be as small as possible, subject to the first and second constraints (it is to be noted that a similar procedure to derive e may be realized with respect to the above methods implemented for the digital predistorter and the envelope tracking module).

[0074] Thus, with reference to FIG. 1, a schematic diagram of an example linearization system 100, comprising a power amplifier 114 whose operational power (and thus non-linear behavior) is controlled based on an envelope tracking signal e produced by an envelope generator (tracker) 140, and based on the system's input signal, u, is shown. In some examples, the envelope tracker/generator 140 is configured to produce an output that takes into account non-linear behavior of various modules of the system 100 (and not only the non-linear behavior of the PA 114), including the non-linear behavior of a power supply modulator 150 that controls the power provided to the power amplifier 114. Thus, for example, the envelope tracker 140 may produce output based on the non-linear characteristics of the power supply modulator (and/or non-linear characteristics of other modules/units of the system 100) with such output either provided directly to the power supply modulator (e.g., to mitigate, in some embodiments, the non-linear behavior of the power supply modulator 150), or provided to the actuator 120 for further processing (as will be discussed in greater detail below). The linearization system 100 includes a transmitter chain 110 used to perform the transmission processing on signals produced by an actuator (implementing a digital predistorter, or DPD) 120. Particularly, in the embodiments of FIG. 1, the transmit chain includes a transmitter and observation path circuitry that includes a digital-to-analog converter 112 (which may optionally be coupled to a frequency modulator/multiplier and/or a variable gain amplifier) that produces an analog signal that possibly has been shifted to an appropriate RF band. The predistorted analog signal (also referred to as predistorted output signal) is then provided to the power amplifier 114 whose power is modulated by a signal e.sub.B (which may be the actual supplied voltage to power the PA, or a signal representative of the voltage level to be applied to the PA) determined based on an envelope tracking signal e.sub.A produced by the actuator 120 based on the input signal u. As will be discussed in greater detail below, in some embodiments, a modulation signal e.sub.A, produced by the actuator 120, may take into account the behavior of the input signal u, the predistortion functionality of the actuator 120, characteristics of the power supply modulator 150 (including any non-linear characteristics of the power supply modulator), and characteristics of the PA 114 (including the PA's non-linear profile) in order to produce the modulating signal, e.sub.B, to modulate the PA 114 in a more optimal way that depends not only on the signal u, but also on the desired predistortion and non-linear behaviors of the system 100. The output signal, w, produced by the PA 114, is a process (e.g., amplified) signal in which, ideally (depending on the effectiveness of the predistortion functionality implemented by the actuator 120 and the non-linear behavior of the PA regulated through the control signal e.sub.B), non-linear distortion of the output signal has been substantially removed. In some embodiments, the output signal, w, may be provided to a bandpass filter (not shown in FIG. 1) to remove any unwanted harmonics or other signal noise, before being communicated to its destination (a local circuit or device, or a remote device) via a wired or wireless link. It is to be noted that to the extent that the envelope tracker/generator 140 may be configured to model the non-linear behavior of either the PA 114 and/or the power supply modulator 150, the sampling rate for the signal e.sub.A may be controlled (e.g., be increased) so that it can better track/monitor frequency expansion resulting from the non-linear behavior of power supply modulator and/or other modules of the system 100. e.sub.A may have a sampling rate of, for example, 10 msps, 100 msps, or any other appropriate sampling rate.

[0075] As also shown in FIG. 1, the transmitter chain 110 includes an observation path to measure the output signal produced by the PA 114 in order to perform the DPD adaptation process (discussed in greater detail below). In some embodiments, the observation path circuitry includes a frequency demodulator/multiplier (e.g., which may be part of a coupler 116 schematically depicted in FIG. 1) whose output is coupled to an analog-to-digital converter (ADC) 118 to produce the digital samples used in the DPD adaptation process implemented by an estimator 130. The estimator 130 is configured to, for example, compute coefficients that weigh basis functions selected to perform the predistortion operation on the input signal u. It is to be noted that while the signals u and e.sub.A can have different sampling rates, the feedback signals y and e.sub.B (i.e., the signal modulating the power level of the PA) generally need to be provided at the same sampling rate for proper basis reconstruction. The estimator 130 derives the DPD coefficients based (at least indirectly) on the amplitude variations of the input signal u (provided to the actuator 120 and the envelope tracker 140). Particularly, because the envelope tracker 140 produces a signal that corresponds to the amplitude variations of the input signal u, and that signal is used to control the non-linear behavior of the PA, which in turn impacts the output of the transmit chain, the coefficients derived by the estimator 130 are affected by the amplitude variation behavior tracked by the envelope tracker 140.

[0076] In addition to producing coefficients to weigh the predistortion components/functions, the estimator 130 may also be configured to derive coefficients that weigh functions applied to the envelope tracking signal e (in embodiments in which the signal e produced by the envelope tracker 140 is provided directly to the actuator 120, as occurs in the system 100 of FIG. 1) to produce a resultant control signal e.sub.A that controls/modulates an envelope tracking power supply modulator 150 to control or modulate power provided to operate the PA 114 of the system 100. More particularly, as noted, the envelope tracker/generator 140 is configured to generate an envelope signal e which is appropriate for the given input baseband signal u and for the power amplifier implementation in order to regulate the operation (including the non-linear behavior) of the PA. As will be discussed in greater detail below, in some embodiments, a modulation signal e.sub.A, produced by the actuator 120, may take into account the behavior of the input signal u, the predistortion functionality of the actuator 120, characteristics of the power supply modulator 150 (including any non-linear characteristics of the power supply modulator), and characteristics of the PA 114 (including the PA's non-linear profile) in order to produce the modulating signal, e.sub.B, to modulate the PA 114 in a more optimal way that depends not only on the signal u, but also on the desired predistortion and non-linear behaviors of the system 100.

[0077] In some embodiments, and as depicted in FIG. 1, instead of directly being supplied to the power modulator 150, the tracked envelope signal e may be directed to the actuator 120, which makes explicit use of the tracked envelope signal e to generate the predistorted signal v. In some embodiments, the signal u (or, alternatively, the intermediate signal v) may also be used to generate the new envelope signal e.sub.A, with the new envelope signal e.sub.A having a bandwidth that is compatible with the power supply modulator 150. In some embodiments, the signal e may also be provided (in addition to, or instead of) to the power supply modulator 150.

[0078] Thus, as depicted in FIG. 2, showing an example of the inputs/output configuration for an example actuator 200 (which may be similar to the actuator 120 of FIG. 1), in some embodiments the actuator 200 (DPD engine) receives the input signal u (e.g., a digital signal with 500 Msps) and also receives the tracked envelope signal e generated based on the signal u (with a bandwidth commensurate with the bandwidth of the signal u, e.g., the signal e may also have 500 Msps signal). The actuator 200 predistorts the signal u to generate the predistorted signal v based, in part, on e, with the predistorted signal v having a bandwidth commensurate with the bandwidth of the input signal u (e.g., v may also be a signal with 500 Msps). The actuator also generates the signal e.sub.A, optionally based, in part, on the signal u, with e.sub.A having a bandwidth that is compatible with the bandwidth of the power supply modulator 150. In the example of FIG. 2, the new tracked envelope signal generated based on the signal e (and possibly based on the signal u) has a bandwidth corresponding to 10 Msps (as compared to the much larger 500 Msmp of the predistorted signal v). It is noted that in some implementation the new signal e.sub.A need not be based on the time-varying signal u, but instead may be, for example, a down-sampled version of the signal e, or may otherwise be a resultant signal processed (through some pre-determined filtering process) from the signal e.

[0079] In embodiments where the tracked envelope signal is provided to the actuator 120, the signal e should be large enough to avoid irreversible damage to the baseband signal u caused by clipping, but should also be as small as possible to maximize PA efficiency. Accordingly, in some embodiments, the envelope tracker 140 is implemented to generate a digital envelope signal e=e[t] (for the purposes of the present description, the notation t represents discrete digital samples or instances) that satisfies three (3) main conditions. A first condition is that the inequality e[t]≥h(|u[t]|) has to be satisfied, where the function h(⋅) defines the relation between the instantaneous power of the baseband signal and the power supply, preventing irreparable damage by clipping. This function corresponds to the shaping table used in conventional envelope trackers/generators generating envelope signals that directly regulate the power of the PA in a power amplifier system. An example of function h(⋅) is given by:

[00004]$h\left(.Math.u.Math.\right)=V.Math..Math.\min +\frac{\left(V.Math.\max -V.Math..Math.\min \right).Math..Math.u.Math.}{U.Math.\max }$

where Vmin is the minimal supply voltage for the PA, Vmax is the maximal supply voltage for the PA, and Umax is the maximal possible value of |u[n]|. This constraint can be used to control the voltage range to be controlled by the envelope tracker. Other examples of functions h that establish relations between instantaneous power of a baseband signal and the power supply may be used.

[0080] A second condition or constraint that may be imposed on the signal e generated by the envelope tracker 140 is that e(t) needs to satisfy maximal value and curvature bounds, expressed by the following inequalities:

e[t]≤E0, and |2e[t]−e[t−1]−e[t+1]|≤E2,

where the constants E0, E2 depend on the particular PA used (e.g., E0 and E2 represents operational characteristics, attributes, and behavior of the particular PA 114 used in the transmit chain 110 of FIG. 1). The expression |2e[t]−e[t−1]−e[t+1]|≤E2 is a bounding second derivative and may represent a smoothness constraint. This constraint may be used to control the smoothness of the tracking envelope curve, and thus control the response speed of the envelope tracking to the signal being tracked (e.g., the constraint may be used to control how fast the signal response is; a smoother function, e, will correspond to a slower tracking signal). The pre-determined constant E2 can thus be selected (e.g., by a user) to control the speed of the response of the envelope tracker, and can be representative of the bandwidth characteristics of the PA 114 and/or the envelope tracking power supply modulator 150.

[0081] A third constraint that may be imposed on the signal e[t] is that, subject to the bounds established by the first and second constrains, the values of e[t] should be as small as possible.

[0082] Thus, the envelope tracker/generator is configured to implement a substantially real-time signal processing procedure which conforms to the constraints (1)-(3) by, for example, iteratively updating a function g=g(t, α) such that selecting e[t]≥g(t, e [t−1]) is not in conflict with the specifications constraints e[t]≤E0 and e[t]≥2e[t−1]−e[t−2]−E2, and allows future selections of e[τ], with τ>t, to be possible in such a way that to satisfy conditions (1) and (2). The lower bound g(t, α) is specified as a piecewise linear function of its second argument, with break points spaced evenly on the interval [0, e0].

[0083] The signal e[t] determined, based on the input signal u[t] (prior to any predistortion processing applied to u) is provided to the actuator/DPD engine 120 of the system 100 depicted in FIG. 1. As noted, the actuator 120 may generate two output signals: i) a predistorted signal v[t], which is derived based on the input signal u (which is a digital signal that can be represented as u[t]) and the time-varying envelope tracking signal e[t] (whose samples depend on the amplitude variations of the signal u[t]), and ii) the resultant envelope tracking signal e.sub.A[t] which may also be derived based on the input signal u[t] and the envelope tracking signal e[t] and therefore can factor into the modulating signal (controlling the PA) the behavior of the input signal u[t]. By basing both the resultant predistorted signal v[t] and the power supply modulation signal e.sub.A[t] on the input signal u[t] and the envelope tracking signal e[t] (with the tracking signal being derived based, in part, on the particular characteristics, as represented by the values E0 and E2, of the PA to be regulated), the PA can be carefully regulated to control its non-linear behavior in a way that would allow a more optimal processing of the predistorted signal. Put another way, higher efficiency (e.g., in terms of power consumption and bandwidth characteristics) may be achieved by deliberately setting the PA to operate in a non-linear mode (e.g., by under-powering the PA, to reduce power consumption) that is mitigated/countered through predistortion processing of the input signal u[t] that depends on the particular non-linear behavior point selected for the PA. Accordingly, in such embodiments, the actuator 120 is configured to perform the digital predistortion by using the time-varying control signal e in the digital predistortion of the input signal u such that the output of the transmit chain resulting from the input signal u and actuated by the control signal e is substantially free of the at least some non-linear distortion caused by the generated control signal.

[0084] Different predistortion processing may be implemented by the actuator 120 to pre-invert the signal. In some example embodiments, the actuator 120 may derive the output v[t] according to the expression:

[00005]$v\left[t\right]=u\left[t\right]+\underset{k=1}{\overset{n}{.Math.}}.Math.x_k.Math.B_k\left(q_u\left[t\right],q_e\left[t\right]\right)$$\mathrm{with}$$q_u\left[t\right]=\left[\begin{array}{c}u\left[t+l-1\right]\\ u\left[t+l-2\right]\\ \mathrm{.Math.}\\ u\left[t+l-\tau \right]\end{array}\right]$$\mathrm{and}.Math..Math.\mathrm{with}$$q_e\left[t\right]=\left[\begin{array}{c}e\left[t+s\left(l-1\right)\right]\\ e\left[t+s\left(l-2\right)\right]\\ \mathrm{.Math.}\\ e\left[t+s\left(l-\tau \right)\right]\end{array}\right]$

[0085] In the above expression, B.sub.k are the basis functions, q.sub.u[t] and q.sub.e[t] are the stacks of recent (around t) baseband and envelope input samples, respectively, s is a time scale separation factor, which is a positive integer reflecting the ratio of time constants of the PA's power modulator and the PA, and x.sub.k are complex scalars of the coefficients of the compensator x∈.sup.n. The estimator 130 (i.e., adaptation unit) illustrated in FIG. 1 adjusts the coefficients x.sub.k of the actuator by observing the measurement samples y[t] (observed from the output signal w(t) of the PA 114) and may minimize the regularized mean squared error. This can be solved, for example, by any minimization technique such as a least-squares method, a stochastic gradient method, etc. The optimization of the adjustable (adaptive) coefficients may further be based, for example, on the intermediate signal v, the modulating control signal e.sub.B, and/or the control signal e.sub.A.

[0086] Similarly, the output signal e.sub.A[t] may be derived using an optimization process, (which may also be implemented using the estimator 130) based on the input signal u, the control signal e, and the feed-back (observed) signals e.sub.B and y provided to the estimator 130. For example, in situations where the envelope tracking power supply modulator 150 exhibits non-linear behavior (i.e., the relationship between the power supply modulator's output signal e.sub.B and its input signal, e.sub.A, is non-linear), the signal e.sub.A may be produced through digital predistortion processing applied to the signals u and e, that achieves some optimization criterion (e.g., to match e to e.sub.B). Alternatively, in some embodiments (e.g., when the power supply modulator exhibits substantially linear behavior), processing performed by the actuator 120 to produce the signal e.sub.A may depend only on the signal e (e.g., e.sub.A may be a downsampled version of e, with a bandwidth that is compatible with the bandwidth of the envelope tracking power supply modulator 150) without needing to take the signal u (or some other signal) into account.

[0087] Examples of procedures/techniques to derive coefficients (parameters) for weighing basis functions selected for predistortion operations (be it for predistortion operations on a baseband input signal such as u, or on an envelope tracking signal e to modulate a power supply powering a power amplifier) are described in U.S. patent application Ser. No. 16/004,594, entitled “Linearization System,” the content of which is incorporated herein by references in its entirety. Briefly, output signal, v, which is provided as input to the transmit chain 110, is generated, based on the input signal u (or, in the embodiments of the systems depicted in FIGS. 1 and 2, the input signal may include a combination of the baseband signal u and the output, e, of an envelope tracker), to include an “inverse nonlinear distortion” (i.e., an inverse of the nonlinear distortion introduced by the transmit chain 110), such that the nonlinear distortion introduced by the transmit chain 106 is substantially cancelled by the inverse nonlinear distortion. The output signal, w is therefore substantially free of nonlinear distortion.

[0088] In some examples, a DPD (such as the actuator 120) operates according to an inverse model of the nonlinear distortion of the transmit chain (e.g., the transmit chain 110 of FIG. 1) such that providing the input signal, u, to the DPD causes the DPD/actuator to generate the intermediate input signal, v as follows:

[00006]$v=2.Math.u+\underset{i=1}{\overset{n}{.Math.}}.Math.x_i.Math.f_i\left(u\right)$

where f.sub.i(⋅) is the i.sup.th basis function of n basis functions and x.sub.i is the i.sup.th parameter (e.g., the i.sup.th weight) corresponding to the i.sup.th basis function. Each basis function is a linear function (e.g., u(t−1)) or a non-linear function (e.g., |u(t)|.sup.2) of the input, u, which may include memory (e.g., u(t)*u(t−1)).

[0089] To update the parameters, x, used by, for example, the actuator (DPD processor) 120 of FIG. 1, a predictor module (such as the estimator 130 of FIG. 1) processes the input signal to the transmit chain, i.e., the signal v, corresponding the predistorted output of the actuator 120, and a sensed version (e.g., a signal b) of the output signal w of the transmit chain (or some other output module that is downstream of the transmit chain) to generate an updated set of parameters, x′. The sensed signal b is observed via an observation receiver/coupler (such as the coupler 116 of FIG. 1) coupled to the output of a transmit chain. In some embodiments, a synchronizer (not shown) may be used to synchronize or correlate the signals used for the adaptation processes.

[0090] In one example, the predictor module determines an updated set of parameters x′ that, in combination with the basis functions and the intermediate input signal, v, generate a predicted signal that is as close as possible to the sensed signal, b (e.g., in a least mean squared error sense). This can be restated as:

[00007]$P\left(v\right)=\underset{i=1}{\overset{n}{.Math.}}.Math.x_i.Math.f_i.Math.\left(v\right)$

[0091] The predictor, P, may be provided to the actuator 120 to update the actuator's coefficients. In some examples, for the predictor P described above, the adaptation processor 130 configures the actuator (digital predistorter) 120 to perform according to an approximate inverse of the predictor P as follows:

[00008]$D.Math.P.Math.D\left(u\right)=P^{-1}\left(u\right)\approx 2.Math.u-\underset{i=1}{\overset{n}{.Math.}}.Math.x_i.Math.f_i\left(u\right)$

Alternatively, the DPD parameters may be set as: a.sub.i=−α.sub.i.

[0092] In another example, the predictor module may be configured to determine an updated set of coefficients {circumflex over (α)} that, in combination with the basis functions and the sensed signal, b, generate a predicted signal, that is as close as possible (e.g., in a least mean squared error sense) to the intermediate predistorted signal, v. This can be restated as:

[00009]$P\left(b\right)=\underset{i=1}{\overset{n}{.Math.}}.Math.x_i.Math.f_i.Math.\left(b\right)$

[0093] That is, in such embodiments, P is an estimate of a (post) inverse of the nonlinearity of the transmit chain. In some examples, the adaptation processor 130 configures the actuator 120 according to the predictor P as follows:

[00010]$D.Math.P.Math.D\left(u\right)=P\left(b\right)=\underset{i=1}{\overset{n}{.Math.}}.Math.x_i.Math.f_i\left(b\right)$

or essentially a.sub.i=α.sub.i.

[0094] In another example, updating of the DPD parameters/coefficients may be implemented to generate an updated set of parameters, x′, that, in combination with the basis functions, represent a difference between the model of the nonlinear input/output characteristic of the transmit chain and the current nonlinear input/output characteristic of the transmit chain. In one example, the predictor module determines parameters x that, in combination with the basis functions and the input signal, u, to the DPD (rather than using the intermediate signal v) generate a predicted signal, {circumflex over (b)} that is as close as possible to the sensed signal, b (e.g., in a least mean squared error sense), which can be restated as:

[00011]$P\left(u\right)=\underset{i=1}{\overset{n}{.Math.}}.Math.x_i.Math.f_i\left(u\right).$

[0095] The parameters, x, in combination with the basis functions represent the difference between the model of the nonlinear input/output characteristics of the transmit chain, and the actual nonlinear input/output characteristic of the transmit chain because the effects both the DPD and the transmit chain on the input signal are represented in the sensed signal b. An output of the predictor module, i.e., P, is provided to a DPD update module which processes the predictor P to update the digital predistorter. In some examples, the actuator combines an approximate inverse of the predictor with the existing DPD according to a.sub.i′←a.sub.i+α.sub.i. This essentially approximates a cascade of the approximate inverse of the predictor, P.sup.−1, with the previous DPD configuration to yield the new DPD configuration.

[0096] In another example, the predictor module (estimator) determines a set of parameters x that, in combination with the basis functions and the sensed signal, b, generate a predicted signal, û that is as close as possible to the input signal, u (e.g., in a least mean squared error sense), which can be restated as:

[00012]$P\left(b\right)=\underset{i=1}{\overset{n}{.Math.}}.Math.x_i.Math.f_i\left(b\right).$

[0097] In some implementations, derivation of the coefficients x for weighing the basis functions used by the digital predistorter implementation of the actuator 120 may be determined in batches using a least-squares process as follows:

α=arg min|Aα−b|.sub.2.sup.2=arg min(α.sup.HA.sup.HAα−2A.sup.Hbα+b.sup.Hb)

where b is a vector of sensed signal samples and A is a matrix where each column includes the samples of the basis function, f.sub.i(u). The solution for x is therefore:

x=(A.sup.HA).sup.−1A.sup.Hb.

That is, in this formulation, the samples of the sensed signal and the basis functions are used once for the batch, and not used in subsequent determination of future coefficient values x.

[0098] The reliability of the computed coefficients, x, can vary based on the desired accuracy (or other performance metric), and the computing resources available. In some embodiments, regularization may be used as a criterion for determining the coefficient values to bias the result away from coefficient values with large magnitudes. In some examples, robustness, reliability, and/or convergence of solutions of the coefficients, x, can be improved by incorporating a history of previous batches of the input as follows:

[00013]$x=\underset{\varkappa }{\arg .Math..Math.\min }.Math.\left\{\begin{array}{c}{x}^H\left[\left(1-\lambda \right).Math.\underset{i=1}{\overset{n}{.Math.}}.Math.{\lambda }^{n-i}.Math.A_i^H.Math.A_i\right].Math.x\\ -2.Math.\left(1-\lambda \right).Math.\underset{i=1}{\overset{n}{.Math.}}.Math.{\lambda }^{n-i}.Math.A_i^H.Math.b_{i^{\varkappa }}\\ +\underset{i=1}{\overset{n}{.Math.}}.Math.b_i^H.Math.b_i\\ +\rho .Math..Math.{\varkappa }^H.Math.x\end{array}\right\}$

where A.sub.i and b.sub.i correspond to inputs and outputs for batch i=1, . . . and x depends on the samples from all batches 1 to n. The above equation is subject to x.sub.L≤x≤x.sub.U, 0<λ<1, and ρ>0.

[0099] In the above optimization problem, the large batch term (a Gramian), A.sup.HA may be replaced with

[00014]$\left(1-\lambda \right).Math.\underset{i=1}{\overset{n}{.Math.}}.Math.{\lambda }^{n-i}.Math.A_i^H.Math.A_i,$

which is a “memory Gramian.” Use of the memory Gramian improves the convergence properties of the optimization process, safeguards against glitches in system behavior, and improves overall performance of the system.

[0100] Another example approach to implement determination of DPD parameters is described in U.S. Pat. No. 9,590,668, entitled “Digital Compensator,” the content of which is hereby incorporated by reference in its entirety. Briefly, with reference to FIG. 3, a block diagram of an adjustable pre-distorting power amplifier system 300, which may be similar to, or include, the portion of the system 100 comprising the actuator 120 (implementing a DPD processor), the transmit chain 110, and the estimator (predictor module) 130 of the system 100 of FIG. 1, is shown. In the example system 300, a digital input signal x[m] at a baseband or intermediate frequency is passed through a Digital Pre-Distorter (DPD) 310 (which may be similar, in implementation or functionality, to the DPD processing implementation of the actuator 130) to produce a “pre-distorted” input y[m], which is passed through a transmit chain 340 to produce a driving signal v(t) that drives an antenna 350. The transmit chain may include a Digital-to-Analog Converter (DAC) 342, an analog lowpass filter (LPF) 344, and a modulator 346 (e.g., multiplication by a local oscillator) of the output of the LPF 344. The output of the modulator is passed to a power amplifier (PA) 348.

[0101] The DPD 310 may be controlled using a controller to determine/compute DPD coefficients (shown as DPD coefficients Θ 320) to adjust the DPD 310 using those determined DPD coefficients. In some embodiments, the DPD coefficients Θ 320 are determined using a database of coefficients 330, and values that essentially characterize the operation “regime” (i.e., a class of physical conditions) of the transmit chain, and/or of other system components (including remote load components and load conditions). These values (e.g., quantitative or categorical digital variables) include environment variables 332 (e.g., temperature, transmitter power level, supply voltage, frequency band, load characteristics, etc.) and/or a part “signature” 334, which represents substantially invariant characteristics, and which may be unique to the electronic parts of the transmit chain 340.

[0102] Determined system characteristic values or attributes may be provided to a coefficient estimator/interpolator 336 (e.g., via a feedback receive chain 360). The determined characteristics and metrics may be used to estimate/derive appropriate DPD coefficients. For example, the DPD coefficient sets may be computed so as to achieve some desired associated distortion measures/metrics that characterize the effects of the preprocessing, including an error vector magnitude (EVM), an adjacent channel power ratio (ACPR), operating band unwanted emissions (OBUE) or other types of distortion measures/metrics.

[0103] The coefficient interpolator 336 uses the various inputs it receives to access the coefficient database 332 and determine and output the corresponding DPD coefficients 320. A variety of approaches may be implemented by the coefficient estimator/interpolator 336, including selection and/or interpolation of coefficient values in the database according to the inputs, and/or applying a mathematical mapping of the input represented by values in the coefficient database. For example, the estimator/interpolator 336 may be configured to select, from a plurality of sets of DPD coefficients (in the database 330), a DPD coefficient set associated with one or more pre-determined system characteristics or some metric derived therefrom. The DPD coefficients used to control/adjust the DPD 310 may be determined by selecting two or more sets of DPD coefficients from a plurality of sets of DPD coefficients (maintained in the database 330) based on the system characteristics. An interpolated set of DPD coefficients may then be determined from the selected two or more sets of DPD coefficients.

[0104] Turning back to FIG. 1, the envelope tracking power supply modulator 150 modulates the power supplied to the PA 114 using the resultant modulating signal e that was derived, by the actuator 120, based on the envelope tracking signal e[t] and optionally the input signal u. The PA 114, whose power is modulated by e.sub.B (e.g., the modulator 150, which may be implemented using shaping table or through some other realization, produces the output control signal, e.sub.B, responsive to the modulating input e.sub.A[t]), processes the predistorted intermediate signal v[t] to produce an output signal w(t) that is substantially free of predistortion that would otherwise have occurred had u[t] not been predistorted. As noted, by controlling the intermediate signal v and the modulating signal e.sub.A[t], the PA can be actuated to operate in a particular non-linear manner (or profile) that can more optimally process the predistorted intermediate signal v[t] (e.g., use less power). As depicted in FIG. 1, the signal e.sub.A[t] produced by the actuator 120 has a bandwidth that is compatible with the bandwidth that can be handled by the envelope tracking power supply modulator 150. Thus, if, as shown in the example of FIG. 1, the modulator 150 has a maximum bandwidth of 10 MHz, the actuator 120 may be configured to produce a signal e.sub.A[t] with 10 Msps.

[0105] The system 100 illustrated in FIG. 1 may be at least part of a digital front end of a device or system (such as a network node, e.g., a WWAN base station or a WLAN access point, or of a mobile device). As such, the system 100 may be electrically coupled to communication modules implementing wired communications with remote devices (e.g., via network interfaces for wired network connections such as Ethernet connections), or wireless communications with such remote devices. In some embodiments, the system 100 may be used locally within a device or system to perform processing (predistortion processing or otherwise) on various signals produced locally in order to generate a resultant processed signal (whether or not that resultant signal is then communicated to a remote device).

[0106] In some embodiments, at least some functionality of the linearization system 100 (e.g., generation of an envelope signal, performing predistortion on the signals u and/or e using adaptable coefficients derived through based on one or more of u, e, v, y, e.sub.A and/or e.sub.B depicted in FIG. 1) may be implemented using a controller (e.g., a processor-based controller) included with one or more of the modules of the system 100 (the actuator 120, the estimator (adaptation module) 130, or any of the other modules of the system 100). The controller may be operatively coupled to the various modules or units of the system 100, and be configured to generate an efficient envelope tracking signal e, compute predistorted sample values for v and e.sub.A (the outputs of the actuator 120 or the actuator 200), update the actuator's coefficients, etc. The controller may include one or more microprocessors, microcontrollers, and/or digital signal processors that provide processing functionality, as well as other computation and control functionality. The controller may also include special purpose logic circuitry, e.g., an FPGA (field programmable gate array), an ASIC (application-specific integrated circuit), a DSP processor, a graphics processing unit (GPU), an accelerated processing unit (APU), an application processor, customized dedicated circuitry, etc., to implement, at least in part, the processes and functionality for the system 100. The controller may also include memory for storing data and software instructions for executing programmed functionality within the device. Generally speaking, a computer accessible storage medium may include any non-transitory storage media accessible by a computer during use to provide instructions and/or data to the computer. For example, a computer accessible storage medium may include storage media such as magnetic or optical disks and semiconductor (solid-state) memories, DRAM, SRAM, etc.

[0107] With reference to FIG. 8, a diagram of another example linearization system 800 implemented according to an arrangement comprising an envelope tracking module (envelope generator) 840 that may be similar to the envelope generator 140 of FIG. 1, an actuator 820 that may be similar to the actuator 120 of FIG. 1, and a power supply modulator 850 that may be similar to the power supply modulator 150 of FIG. 1. In the embodiments of FIG. 8, the envelope generator 840 is configured to generate an output e, that is provided directly to the envelope tracking power supply modulator 850 to control the power provided to a PA 814 (of a transmit chain 810, which may be implemented similarly to the transmit chain 110 of FIG. 1). In some embodiments, and assuming the signal e is an analog, continuous signal, the power supply modulator 850 may be implemented as a switched-mode power supply (e.g., multi-level buck converter), in which a decoder is required to convert continuous signal e into digital control lines. One common issue with switched-mode operation is the non-ideal transient step response. This necessitates an accurate power supply predictor and behavioral modeling. Under-sampling e can degrade the accuracy of modeling. Thus, in such embodiments, it may be preferable to over-sample e to model the behavior of the envelope tracking power supply modulator 850 to produce a signal s.sub.p, which would be a faithful representation of s.

[0108] Control of the PA's power based on the control signal e results, in turn, in output behavior in which an output of the PA 814 is provided to an observation chain (via a coupler 816) comprising an ADC 818, to a digital predistorter that includes an estimator 830 and an actuator 820 predistorting an input signal u according to DPD parameters adaptively estimated by the estimator 830. Because the envelope generator 840 is indirectly coupled to the estimator (via the power supply modulator 850, and a supply filter 852, the PA 814, the coupler 816, and the ADC 818), the signal e outputted by the envelope generator 840, affects, at least indirectly, the DPD behavior of the linearization system 800, and the adaptation process implemented by the DPD of the system 800. This allows the system 800 to adapt its predistortion behavior according to the behavior (including the non-linear behavior) of the various modules of the system 800 (i.e., according to the behavior of the transmit chain 810, the power supply modulator 850, and/or the supply filter 852).

[0109] As shown in FIG. 8, in some implementations that linearization system may include the supply filter 852, which may be configured to remove noise, and/or smooth the control or power signal fed into the PA (e.g., in order to prevent sudden power level changes that could damage the PA). The discontinuities in the envelope, as well as quantization and switching noise can cause deterioration of the output spectrum, and degrade the out-of-band noise performance in the system. The filter 852, which may be an analog or digital filter, can be used to mitigate some of the degradation and noise caused by the various other modules/components of the linearization system.

[0110] As noted, the envelope generator 840 may be similar, in its implementation/configuration, to the envelope generator 140 of FIG. 1. Thus, in some examples, the envelope generator 840 may include a receiver to receive the input signal u, with the input signal u also being provided to the digital predistorter (comprising the actuator 820 and the estimator 830) coupled to the transmit chain 810 comprising the power amplifier 814. The envelope generator 840 also include a controller (implemented as a processor-based device or as a non-processor circuit) to determine, based on amplitude variations of the input signal u, the time-varying signal, e, with the amplitude variations of the time-varying signal e corresponding to time variations in non-linear characteristics of the transmit chain. For example, in the embodiments of FIG. 8, the controller of the envelope generator may derive a control signal e that satisfies a set of constraints defined according to one or more parameters (such as the parameters E0 and E2 discussed in relation to the embodiments of the system 100) that represent the behavior (e.g., non-linear behavior) of one or more of the modules/components of the system 800. The signal derived by the controller of the envelope generator can then be outputted by an output section of the envelope generator 840. In the embodiments of FIG. 8, the output signal e is provided, for example, to an input of the power supply modulator 850 (in contrast, in the embodiments depicted for FIG. 1, the control signal e is provided to the actuator 120 of the system 100). As noted, in the embodiments of FIG. 8, and similarly to the embodiments of FIG. 1, the digital predistorter of the system 800 is configured to receive another input signal that depends on the amplitude variations of the time-varying signal e, and to generate, based at least in part on signals comprising the input signal u and the other input signal, a digitally predistorted output, v, provided to the transmit chain 810, to mitigate non-linear behavior of the transmit chain. In some examples, the other input signal may include an observed digital sample (illustrated as the signal y in FIG. 8, with y being the digital output of the ADC 818) of an output of the at least one power amplifier. This other signal, y, along with a copy of the output, v, of the actuator 820, are provided to the estimator 830, which performs an optimization process to compute DPD parameters/coefficients to weigh the basis functions implemented by the predistorter to predistort the input signal u (example optimization processes to compute DPD coefficients are discussed above). Variations (changes) to the time-varying signal e produced by the envelope generator 840 will result in variations/changes to the power provided to the PA 814 (e.g., to intentionally cause the PA to be underpowered, thus resulting in non-linear behavior that can be more efficiently mitigated through adaptation of the system 800's predistorter), which in turn impacts the behavior/nature of the signal outputted by the PA 814, and of the observed sample, y, that is provided to the estimator 830.

[0111] In some embodiments, performance of the linearization system may be improved (e.g., to speed up the response of the envelope signal, and to improve the responsiveness of the adaptation process to variations of the envelope signal) by using a predictor module (which may be implemented as a processor or non-processor circuit) to model and predict the behavior of the power supply modulator of the linearization system (and/or predict the behavior of other modules) Control signal representative of the predicted behavior of the power supply modulator (and/or of other modules of the linearization system) can then be provided directly to, for example, an estimator of the DPD unit in order to derive DPD parameters/coefficients. Predicted modeling of the behavior of various linearization system modules can thus expedite the adaptation process that would otherwise be more slowly performed if it were to rely only on observed downstream signals to derive DPD coefficients. Predictor modules, such as those described herein, can account, for example, for the presence of dynamic power supply switching.

[0112] Accordingly, with reference to FIG. 9, another example implementation of a linearization system 900 that includes a predictor module 942 electrically interposed between an output of an envelope generator 940 (which may be similar, in implementation and configuration, to the envelope generators 140 and 840 of FIGS. 1 and 8, respectively) and a digital predistorter (e.g., the predistorter's estimator 930, which may be similar, in implementation and configuration, to the estimators 130 and 830 of FIGS. 1 and 8, respectively) is shown. The predictor module 942 is configured to model non-idealities that transform the envelope control signal e to the signal s (depicted in FIG. 9 as being the output of the supply filter 952, which, similarly to the supply filter 852 of FIG. 8, may be an analog or digital filter configured to remove quantization and switching noise, and/or smooth the control or power signals provided to the PA 914).

[0113] An example of non-idealities impacting the signaling s resulting from e, and degrading the linearization performance (e.g., the speed of DPD adaptively if the DPD uses a signal depended on s to perform the adaptation/optimization process producing DPD coefficients) can include, for example, time misalignment between v (the output of the actuator 920) and s (the output of the supply filter), non-linearities resulting from operational characteristics of active components of the various modules, etc. Modelling of non-idealities can be based on linear or non-linear transformations that map values of e to expected values of s (or values of other downstream signaling affected by the values of e). Output of the predictor module can then be provided to the estimator to derive, based on the output of the predicted values (in conjunctions with one or more of the base band input signal u and the sampled values y), DPD parameters to predistort the input signal u. Thus, the embodiments of FIG. 9 realize an actuator (e.g., the actuator/predistortion block 920) that depends at least on the input base band signal u, and a predicted power supply waveform s.sub.p, matching the appropriate degree of accuracy to s. Such implementations can generate optimal or near-optimal linearization results while maintaining high power efficiency by modeling the nonlinear PA and predistortion as two inputs and one output system. In some of the example embodiments of FIG. 9, the envelope generator (envelope tracking module) may thus be configured to provide the time-varying signal e to the predictor module (electrically interposed between the envelope tracking module and the digital predistorter) configured to compute the predicted signal, s.sub.p, representative of an estimated expected behavior of the power supply modulator (controlling electrical operation of the transmit chain) based on known characteristics of the power supply module and the determined time-varying signal e. In such embodiments, the other input signal of the digital predistorter may include the predicted signal, s.sub.p, computed by the predictor module.

[0114] As further shown in the system arrangement of FIG. 9, the output of the envelope generator 940 may also be provided to the power supply modulator 950 (in addition to being provided to the predictor module 942). However, in some embodiments, the power supply modulator may receive control input from the actuator (e.g., similarly to the arrangement depicted in FIG. 1, where, the power supply modulator 150 receives a signal e.sub.A produced by the actuator 120) in addition to, or instead of, receiving the signal e. In such embodiments, a control signal to control the power supply modulator may be generated using a transformation (optionally an adaptive transformation) that is based on the non-linear characteristics of the power supply modulator 950 and/or any other module, component, or section of the linearization system 900. The power supply modulator generates a power signal (or a control signal to control power provided by a separate power supply unit; not shown in FIG. 9), which in turn is provided to the supply filter 952 that performs noise removal and conditioning operation on the signal provided by the power supply modulator to produce the signal s (which may be the actual power signal, or may be a control signal controlling a power supply unit providing the electrical power to the PA 914).

[0115] As also shown, the base band signal u is processed by the actuator 920, which predistorts the signal u to produce a predistorted signal v. In some embodiments, the processing of the signal u may include a decomposition of the signal into a basis functions representation that is weighed by adaptive coefficients (derived based at least on the output of the transmit chain, provided to the estimator 930 via a coupler 916 and an ADC 918), and/or the predicted signals produced by the predictor module 942). In some embodiments, the use of the predicted signal s.sub.p allows the derivation of DPD coefficients that are configured for optimal or near-optimal operation with the power supply modulator 950. For example, the power supply modulator may be controlled (via the signal e computed by the envelope generator 940) to be intentionally operated in a non-linear manner that can be mitigated through appropriate computation of DPD coefficients, derived based, in part, on the predicted signal s.sub.p shown in FIG. 9, that counter the non-linear operation of the transmit chain 910.

[0116] With reference next to FIG. 4, a flowchart of an example procedure 400 for digital predistortion is shown. The procedure 400 includes receiving 410, by a digital predistorter (e.g., by a receiver section of a digital predistorter device such as the actuators 120 or 200 depicted in FIGS. 1 and 2), a first signal that depends on amplitude variations based on an input signal, u, with the variations of the first signal corresponding to time variations in non-linear characteristics of a transmit chain such as the transmit chain 110 depicted in FIG. 1) that includes a power amplifier.

[0117] In some embodiments, the first signal may correspond to a time varying signal e generated by an envelope tracker (such as the tracker 140 of FIG. 1), in which case, receiving the first signal may include monitoring, by the digital predistorter, a time-varying signal e generated by an envelope tracker that received a copy of the input signal u. The signal e tracks the shape of the envelope of the signal u, and thus e depends on amplitude variations of the input signal u. In some examples, the procedure 400 may further include filtering the time-varying signal e.

[0118] As noted, in some embodiments, the time-varying control signal e may be determined according to an optimization process that is based on characteristics of the transmit chain, and with the resultant control signal being based on parameters that can be adjusted or selected based on desired behavior of the transmit chain and/or the envelope tracking signal. For example, the determined tracking signal e can be one whose response speed to variations of the input signal can be adjusted (so that the response can be varied from slow to fast). A fast-responding envelope tracking control signal to modulate the power supply modulator (controlling power to the transmit chain) may result in a more efficient modulator (because the power provided to the transmit chain will more closely follow variations to the input signal u, thus reducing power waste), but may require more of a computational effort to derive. In another example, the determined control signal e may be one that is more compatible with the bandwidth of the transmit chain. Thus, in some embodiments, determining the control signal e may include determining the time varying-control signal e satisfying a set of constrains, including: i) a first constraint in which e[t]≥h(|u[t]|), where h(⋅) defines a relation between instantaneous power of the signal u and a power supply of the transmit chain, ii) a second constraint imposing maximal value and curvature bounds for the signal e[t], such that e[t]≤E0, and |2e[t]−e[t−1]−e[t+1]|≤E2, where E0 and E2 are values representative of operational characteristics of the transmit chain, and iii) a third constraint requiring that values of e[t] be as small as possible, subject to the first and second constraints. The value E2 may, for example, be representative of a bandwidth of the transmit chain and/or a response speed of the transmit chain to variations in amplitude of the input signal u.

[0119] With continued reference to FIG. 4, the procedure 400 additionally includes receiving 420, by the digital predistorter (e.g., by the receiver section of the digital predistorter device), the input signal u, and generating 430, by the digital predistorter (e.g., by a controller circuit of the digital predistorter device), based at least in part on signals comprising the input signal u and the first signal, a digitally predistorted signal v to mitigate the non-linear behavior of the transmit chain.

[0120] In examples in which the first signal received by the digital predistorter is the time-varying signal e, the time-varying signal e may generated from the input signal u such that the time-varying signal e causes at least some non-linear behavior of the power amplifier. In such embodiments, generating the digitally predistorted signal v may include using the time-varying signal e to digitally predistort the input signal u such that the output of the transmit chain resulting from digitally predistorting the input signal u is substantially free of the at least some non-linear distortion caused by the time-varying signal e. The signal e may be generated so as to, for example, underpower the power amplifier to controllably cause non-linear behavior that can be mitigated through the predistortion operations of a digital predistorter (e.g., the actuator 120 of FIG. 1), with the predistortion operation being adapted in accordance with the input signal u and the control signal e (i.e., the predistortion operations are based on knowledge of the control signal e that is causing the non-linear behavior, thus potentially resulting in a more efficient joint operation of the envelope tracker, the power supply modulator, the transmit chain, and/or the digital predistorter).

[0121] As noted, in some embodiments, the digital predistortion operations (by the actuator 120) are based on the bandpass input signal u, and the envelope tracking control signal e, thus allowing the predistortion to take into account (at least implicitly) the power modulation of the transmit chain. Accordingly, performing the digital predistortion on the combined signal may include performing the digital predistortion on the combined signal comprising the input signal u and the time-varying control signal e to produce the digitally predistorted signal v according to:

[00015]$v\left[t\right]=u\left[t\right]+\underset{k=1}{\overset{n}{.Math.}}.Math.x_k.Math.B_k\left(q_u\left[t\right],q_e\left[t\right]\right)$$\mathrm{with}$$q_u\left[t\right]=\left[\begin{array}{c}u\left[t+l-1\right]\\ u\left[t+l-2\right]\\ \mathrm{.Math.}\\ u\left[t+l-\tau \right]\end{array}\right]$$\mathrm{and}.Math..Math.\mathrm{with}$$q_e\left[t\right]=\left[\begin{array}{c}e\left[t+s\left(l-1\right)\right]\\ e\left[t+s\left(l-2\right)\right]\\ \mathrm{.Math.}\\ e\left[t+s\left(l-\tau \right)\right]\end{array}\right]$

In such embodiments, B.sub.k are basis functions, q.sub.u[t] and q.sub.e[t] are stacks of recent baseband and envelope input samples, respectively, s is a time scale separation factor representative of a ratio of time constants of the power amplifier and a modulator powering the power amplifier, and x.sub.k are computed coefficients to weigh the basis functions. In some examples, the procedure 400 may further include computing, according to an optimization process that is based, at least in part, on observed samples of the transmit chain, the computed coefficients x.sub.k to weigh the basis functions B.sub.k.

[0122] In some embodiments, the procedure 400 may also include generating a resultant envelope tracking signal, e.sub.A, through digital predistortion performed on the combined signal comprising the input signal u and the time-varying control signal e, to mitigate non-linear behavior of a power supply modulator that is producing output, based on the resultant envelope tracking signal, e.sub.A, to modulate the power provided to the power amplifier of the transmit chain. In such embodiments, e.sub.A has a lower bandwidth than the time-varying control signal e. In some embodiments, the signal e.sub.A (produced by the actuator 120) may depend only on the signal e. For example, the signal e.sub.A may simply be a down-sampled signal required for compatibility with the power supply modulator. In such embodiments, the procedure 400 may thus also include generating a resultant envelope tracking signal, e.sub.A, as a function of the time-varying control signal e, with e.sub.A having a lower bandwidth than the time-varying control signal e, and with e.sub.A, provided to a power supply modulator producing output, based on the resultant envelope tracking signal, e.sub.A, to modulate the power provided to the power amplifier of the transmit chain. In some examples, generating the resultant envelope tracking signal e.sub.A may include down-sampling the time-varying control signal e to generate a resultant down-sampled envelope tracking signal, e.sub.A.

[0123] Turning back to FIG. 4, as shown, the procedure 400 further includes providing 440 (e.g., by an output section of a digital predistorter device) the predistorted signal v to the transmit chain (whose non-linear behavior depends, at least in part, on amplitude variations of the signal u, as represented by the signal e or e.sub.A). In some examples, the procedure 400 may further include computing samples of the digitally predistorted signal, v, provided to the transmit chain, as a non-linear function of samples of the input signal u and the first signal.

[0124] In some examples, receiving by the digital predistorter the first signal may include receiving an observed digital sample, y, of an output of the power amplifier controlled by a power supply modulator controlling electrical operation of the transmit chain according to a time-varying signal e generated by an envelope tracker that receives a copy of the input signal u. In some embodiments, receiving by the digital predistorter the first signal may include receiving a predicted signal, s.sub.p, computed by a predictor module electrically interposed between an envelope tracker and the digital predistorter, the predicted signal being representative of an estimated expected behavior of a power supply modulator, controlling electrical operation of the transmit chain, based on known characteristics of the power supply module and a time-varying signal, e, determined by the envelope tracker.

[0125] With reference now to FIG. 5, a flowchart of an example procedure 500 to control electrical operation of a transmit chain (via the generation of envelope tracking control signal) is provided. The procedure 500 is generally performed by an envelope tracking module (envelope generator, such as the envelope generator 140 of FIG. 1). As shown, the procedure 500 includes receiving 510 by the envelope tracking module (e.g., by a receiver/receiver section of an envelope tracking module) an input signal u. The input signal u is further provided to a digital predistorter (e.g., the actuator 120) coupled to the transmit chain (such as the transmit chain 110), with the transmit chain comprising a power amplifier (e.g., the PA 114 of FIG. 1).

[0126] The procedure 500 further includes determining 520, by the envelope tracking module (e.g., by a controller of the envelope tracking module), based on amplitude variations of the input signal u, a time-varying signal, e, with the amplitude variations of the time-varying signal e corresponding to time variations in non-linear characteristics of the transmit chain. The procedure 500 further includes outputting 530, by the envelope tracking module (e.g., by an output section of the envelope tracking module), the time-varying signal e. The digital predistorter is configured to receive another input signal that depends on the amplitude variations of the time-varying signal e, and to generate, based at least in part on signals comprising the input signal u and the other input signal, a digitally predistorted output, v, provided to the transmit chain, to mitigate non-linear behavior of the transmit chain.

[0127] In some examples, determining the time-varying signal, e, may include determining the time-varying signal e to cause a power supply modulator controlling the electrical operation of the transit chain to underpower the power amplifier so as to cause the transmit chain to operate in a non-linear mode. Thus, in some embodiments of FIG. 5, the transmit chain may intentionally be controlled to operate in a non-linear mode (in this example, through underpowering the transmit chain, although in other embodiments, the transmit chain may be placed in non-linear mode by other means, such as overpowering the transmit chain) since the non-linear effects may be efficiently corrected through the digital predistorter of the system, while the underpowering can conserve power and prolong the life of the components of the linearization system.

[0128] In the procedure 500, determining the time-varying signal, e, may include deriving the time-varying signal, e, according to one or more constraints representative of characteristics of the transmit chain. Deriving the time-varying signal e may include deriving the time-varying signal e satisfying a set of constraints that includes a first constraint in which e[t]≥h(|u[t]|), where h(⋅) defines a relation between instantaneous power of the input signal u and a power supply of the transmit chain, a second constraint imposing maximal value and curvature bounds for the signal e, such that e[t]≤E0, and |2e[t]−e[t−1]−e[t+1]|≤E2, where E0 and E2 are values representative of operational characteristics of the power amplifier, and a third constraint requiring that values of e[t] be as small as possible, subject to the first and second constraints.

[0129] In some examples, the parameter E2 may be representative of one or more of, for example, a bandwidth of the transmit chain, or a response speed of the transmit chain to variations in amplitude of the input signal u. Thus, by selecting/varying the parameter E2, the response speed of the envelope tracking signal, and/or its bandwidth, can be controlled. For example, consider the graphs provided in FIGS. 6A-C, which show different envelope tracking responses, each of which may correspond to different values of E2 in the determination of envelope tracking control signal e (the appropriate values of E2 may be determined experimentally or analytically). In FIG. 6A, the graph 600 shows a slow envelope tracking signal 602 that can track the low frequency behavior of a signal 604, but cannot track the fast changing behavior of the signal 604. In this example, the curve 602 (corresponding to the envelope tracking signal) is fairly smooth, and has a relatively small bandwidth. FIG. 6B includes a graph 610 showing a mid-range envelope tracking signal 612, that can track the general shape of the spikes in a signal 614, but still has some noticeable deviations between the shape of the tracking envelope 612 and the signal 614. In this example, the envelope can follow some of the higher frequency components of the signal 614, and accordingly is not as smooth as the curve 602 of FIG. 6A. Lastly, FIG. 6C includes a graph 620 with a fast-response envelope 622, that can more closely follow the variations in a signal 624 than the envelope signals 602 and 612 could. In the example of FIG. 6C, the envelope signal 622 has a relatively large bandwidth, but the signal is less smooth than either of the envelope signals 602 and 612 of FIGS. 6A and 6B, respectively.

[0130] As noted above, in some embodiments, the time-varying signal e may also be provided to the digital predistorter. Thus, the procedure 500 may further include providing, by the envelope tracking module, the time-varying signal e to the digital predistorter. In such embodiments, the other input signal of the digital predistorter may include the time varying signal e. Providing the time-varying signal may include providing the time-varying signal e to the digital predistorter to produce a resultant control signal, e.sub.A, provided to a power supply modulator controlling the electrical operation of the transit chain. The digital predistorter configured to produce the resultant control signal e.sub.A may be configured to compute, based, at least in part, on observed samples of the transmit chain, coefficients to weigh basis functions applied to samples of the input signal u and the time-varying signal e to generate the resultant control signal e.sub.A.

[0131] In the embodiments of FIG. 5 in which the predistorter is provided with the input signal u and the time-varying signal e, the digital predistorter configured to generate the digitally predistorted output, v, may be configured to generate the digitally predistorted output, v, based on the input signal u and the time-varying signal, e, according to:

[00016]$v\left[t\right]=u\left[t\right]+\underset{k=1}{\overset{n}{.Math.}}.Math.x_k.Math.B_k\left(q_u\left[t\right],q_e\left[t\right]\right)$$\mathrm{with}$$q_u\left[t\right]=\left[\begin{array}{c}u\left[t+l-1\right]\\ u\left[t+l-2\right]\\ \mathrm{.Math.}\\ u\left[t+l-\tau \right]\end{array}\right]$$\mathrm{and}.Math..Math.\mathrm{with}$$q_e\left[t\right]=\left[\begin{array}{c}e\left[t+s\left(l-1\right)\right]\\ e\left[t+s\left(l-2\right)\right]\\ \mathrm{.Math.}\\ e\left[t+s\left(l-\tau \right)\right]\end{array}\right]$

with B.sub.k being basis functions, q.sub.u[t] and q.sub.e[t] are stacks of recent baseband and envelope input samples, respectively, s is a time scale separation factor representative of a ratio of time constants of the power amplifier and the power supply modulator powering the power amplifier, and x.sub.k are computed coefficients to weigh the basis functions. The procedure 500 may also include computing according to an optimization process based, at least in part, on observed samples of the transmit chain, the computed coefficients x.sub.k to weigh the basis functions B.sub.k.

[0132] In some examples, the procedure 500 may further include providing the time-varying signal e to a power supply modulator controlling electrical operation of the transmit chain, with the other input signal of the digital predistorter including an observed digital sample, y, of an output of the power amplifier. Such embodiments are illustrated, for example, in FIG. 8. In some embodiments, the procedure 500 may further include providing the time-varying signal e to a predictor module electrically interposed between the envelope tracking module and digital predistorter, the predictor module configured to compute a predicted signal, s.sub.p, representative of an estimated expected behavior of a power supply modulator, controlling electrical operation of the transmit chain, based on known characteristics of the power supply module and the determined time-varying signal e, wherein the other input signal of the digital predistorter includes the predicted signal, s.sub.p, computed by the predictor module. Such embodiments are illustrated, for example, in FIG. 9.

[0133] Turning next to FIG. 7, a flowchart of another example procedure 700, generally performed at a power supply modulator (such as the power supply modulator 150 of FIG. 1) of a linearization system (such as the system 100 of FIG. 1) is shown. The procedure 700 includes receiving 710, by a power supply modulator (e.g., by a receiver section of a power supply modulator), one or more control signals.

[0134] The procedure 700 further includes regulating 720 (e.g., by a regulator/controller circuit of the power supply modulator), based on the one or more control signals, power supply provided to a power amplifier of a transmit chain to underpower the power amplifier so that the transmit chain includes at least some non-linear behavior. The at least some non-linear behavior of the transmit chain, resulting from regulating the power supply based on the one or more control signals, is at least partly mitigated through digital predistortion performed by a digital predistorter (e.g., the actuator 120) on signals comprising an input signal, u, provided to the digital predistorter, and on another signal, provided to the digital predistorter, that depends on amplitude variations based on the input signal, u. The variations of the other signal correspond to time variations in non-linear characteristics of the transmit chain.

[0135] In some embodiments, the other signal provided to the digital predistorter includes a time-varying signal e generated by an envelope tracker that receives a copy of the input signal u. As described herein, the time-varying control signal e may be derived based on a set of constraints, including a first constraint in which e[t]≥h(|u[t]|), where h(⋅) defines a relation between instantaneous power of the input signal u and a power supply of the transmit chain, a second constraint imposing maximal value and curvature bounds for the signal e, such that

e[t]≤E0, and |2e[t]−e[t−1]−e[t+1]|≤E2,

where E0 and E2 are values representative of operational characteristics of the power amplifier, and a third constraint requiring that values of e[t] be as small as possible, subject to the first and second constraints. As noted, E2 may be representative of one or more of, for example, a bandwidth of the transmit chain, and/or a response speed of the transmit chain to variations in amplitude of the input signal u.

[0136] In some embodiments, receiving the one or more control signals may include receiving a time-varying control signal, e.sub.A, derived based, at least in part, on the time-varying signal e, with e.sub.A having a lower bandwidth than the time-varying signal e. Receiving the time-varying signal e.sub.A may include receiving the time-varying signal, e.sub.A, generated through digital predistortion performed on multiple signals comprising the input signal u and the time-varying signal e, to mitigate non-linear behavior of the power supply modulator producing output based on the resultant time-varying signal, e.sub.A. In some examples, receiving the time-varying signal e.sub.A may include receiving the time-varying control signal, e.sub.A, generated as a bandwidth lowering function of the time-varying signal e. The bandwidth lowering function may include a down-sampling function applied to the time-varying signal e.

[0137] The digital predistorter may be configured to generate digitally predistorted output signal, v, from the signals comprising the input signal u and the time-varying control signal e, according to:

[00017]$v\left[t\right]=u\left[t\right]+\underset{k=1}{\overset{n}{.Math.}}.Math.x_k.Math.B_k\left(q_u\left[t\right],q_e\left[t\right]\right)$$\mathrm{with}$$q_u\left[t\right]=\left[\begin{array}{c}u\left[t+l-1\right]\\ u\left[t+l-2\right]\\ \mathrm{.Math.}\\ u\left[t+l-\tau \right]\end{array}\right]$$\mathrm{and}.Math..Math.\mathrm{with}$$q_e\left[t\right]=\left[\begin{array}{c}e\left[t+s\left(l-1\right)\right]\\ e\left[t+s\left(l-2\right)\right]\\ \mathrm{.Math.}\\ e\left[t+s\left(l-\tau \right)\right]\end{array}\right]$

with B.sub.k being basis functions, q.sub.u[t] and q.sub.e[t] being stacks of recent baseband and envelope input samples, respectively, s being a time scale separation factor representative of a ratio of time constants of the power amplifier and the power supply modulator powering the power amplifier, and x.sub.k being computed coefficients to weigh the basis functions. The coefficients x.sub.k may be computed according to an optimization process based, at least in part, on observed samples of the transmit chain. In some examples, the coefficients x.sub.k computed according to the optimization process are computed according to the optimization process and further based on an output of the power supply modulator, the output being one of, for example, a voltage provided to the power amplifier, and/or a control signal to cause a corresponding voltage to be provided to the power amplifier.

[0138] In some examples, the other signal provided to the digital predistorter may include an observed digital sample, y, of an output of the power amplifier, the power amplifier being controlled by the power supply modulator according to a time-varying signal e generated by an envelope tracker that receives a copy of the input signal u. In some embodiments, the other signal provided to the digital predistorter may include a predicted signal, s.sub.p, computed by a predictor module electrically interposed between an envelope tracker and the digital predistorter, the predicted signal being representative of an estimated expected behavior of the power supply modulator based on known characteristics of the power supply module and a time-varying signal, e, determined by the envelope tracker.

[0139] The approaches described above may be used in conjunction with the techniques described in PCT Application PCT/US2019/031714, filed on May 10, 2019, titled “Digital Compensation for a Non-Linear System,” which is incorporated herein by reference. For instance, the techniques described in that application may be used to implement the actuator (referred to as the pre-distorter in the incorporated application), and to adapt its parameters, and in particular to form the actuator to be responsive to an envelope signal or other signal related to power control of a power amplifier.

[0140] The above implementations, as illustrated in FIGS. 1-9, are applicable to a wide range of technologies that include RF technologies (including WWAN technologies, such as cellular technologies, and WLAN technologies), satellite communication technologies, cable modem technologies, wired network technologies, optical communication technologies, and all other RF and non-RF communication technologies. The implementations described herein encompass all techniques and embodiments that pertain to use of digital predistortion in various different communication systems.

[0141] In some implementations, a computer accessible non-transitory storage medium includes a database (also referred to a “design structure” or “integrated circuit definition dataset”) representative of a system including some or all of the components of the linearization and envelope tracking implementations described herein. Generally speaking, a computer accessible storage medium may include any non-transitory storage media accessible by a computer during use to provide instructions and/or data to the computer. For example, a computer accessible storage medium may include storage media such as magnetic or optical disks and semiconductor memories. Generally, the database representative of the system may be a database or other data structure which can be read by a program and used, directly or indirectly, to fabricate the hardware comprising the system. For example, the database may be a behavioral-level description or register-transfer level (RTL) description of the hardware functionality in a high-level design language (HDL) such as Verilog or VHDL. The description may be read by a synthesis tool which may synthesize the description to produce a netlist comprising a list of gates from a synthesis library. The netlist comprises a set of gates which also represents the functionality of the hardware comprising the system. The netlist may then be placed and routed to produce a data set describing geometric shapes to be applied to masks. The masks may then be used in various semiconductor fabrication steps to produce a semiconductor circuit or circuits corresponding to the system. In other examples, the database may itself be the netlist (with or without the synthesis library) or the data set.

[0142] Unless defined otherwise, all technical and scientific terms used herein have the same meaning as commonly or conventionally understood. As used herein, the articles “a” and “an” refer to one or to more than one (i.e., to at least one) of the grammatical object of the article. By way of example, “an element” means one element or more than one element. “About” and/or “approximately” as used herein when referring to a measurable value such as an amount, a temporal duration, and the like, encompasses variations of ±20% or ±10%, ±5%, or +0.1% from the specified value, as such variations are appropriate in the context of the systems, devices, circuits, methods, and other implementations described herein. “Substantially” as used herein when referring to a measurable value such as an amount, a temporal duration, a physical attribute (such as frequency), and the like, also encompasses variations of ±20% or ±10%, ±5%, or +0.1% from the specified value, as such variations are appropriate in the context of the systems, devices, circuits, methods, and other implementations described herein.

[0143] As used herein, including in the claims, “or” as used in a list of items prefaced by “at least one of” or “one or more of” indicates a disjunctive list such that, for example, a list of “at least one of A, B, or C” means A or B or C or AB or AC or BC or ABC (i.e., A and B and C), or combinations with more than one feature (e.g., AA, AAB, ABBC, etc.). Also, as used herein, unless otherwise stated, a statement that a function or operation is “based on” an item or condition means that the function or operation is based on the stated item or condition and may be based on one or more items and/or conditions in addition to the stated item or condition.

[0144] Although particular embodiments have been disclosed herein in detail, this has been done by way of example for purposes of illustration only, and is not intended to be limit the scope of the invention, which is defined by the scope of the appended claims. Features of the disclosed embodiments can be combined, rearranged, etc., within the scope of the invention to produce more embodiments. Some other aspects, advantages, and modifications are considered to be within the scope of the claims provided below. The claims presented are representative of at least some of the embodiments and features disclosed herein. Other unclaimed embodiments and features are also contemplated.