Class-S RF transmitter for MRI scanners

Abstract

An analog input signal (X.sub.(n)) is processed by a Peak to Average Ratio Reduction (PARR) block to diminish the difference between peak amplitudes and average amplitudes of the analog input signal (X.sub.(n)). After, a distorted signal (h(n)) having low peak to average amplitude ratio, generated at the PARR block output, is processed by a delta sigma modulation (DSM) block converts the distorted signal (h(n)) into a digitally modulated distorted signal (h_dsm.sub.(n)) with high signal to noise ratio (SNR). Afterwards, the digitally modulated distorted signal (h_dsm.sub.(n)) is corrected and amplified by a Class-D RF power amplifier fed by a feeding signal (env.sub.(n)) generated from a digital correction signal (z_dsm.sub.(n)). As a result, a digitally modulated signal (y(n)) with high signal to noise ratio (SNR) of the analog input signal (X.sub.(n)) is generated at the output of the Class-D RF power amplifier.

Claims

1. A class-S RF transmitter for Magnetic Resonance Imaging (MRI) scanners comprising: a Peak to Average Ratio Reduction (PARR) block having at least a first output and a second output where an analog input signal is split into a plurality of sections in equal time intervals, a distortion coefficient for each section is calculated by dividing a maximum signal value of the each section into a maximum signal value of the analog input signal, the each section is divided into the corresponding distortion coefficient and combined together to obtain a distorted signal, where the distortion coefficients are transformed into a distortion function; a delta sigma modulation (DSM) block converting the distorted signal, fed from the first output, into a digitally modulated distorted signal; a DSM based envelope modulator converting a multiplicative inverse of the distortion function, fed from the second output, into a correction signal; a dynamic supply modulator converting the correction signal into a DC feeding signal; and a class-D RF power amplifier having at least an RF input and a DC input, wherein the digitally modulated distorted signal is applied to the RF input and the feeding signal is applied to the DC input, amplifying the digitally modulated distorted signal via correcting the amplified digitally modulated distorted signal with the feeding signal, and generating a digitally modulated signal having a high signal to noise ratio.

2. A class-S RF transmitter for Magnetic Resonance Imaging (MRI) scanners comprising: a Peak to Average Ratio Reduction (PARR) block having at least a first output and a second output where an analog input signal is split into a plurality of sections in equal time intervals, a distortion coefficient for each section is calculated by dividing a maximum signal value of the analog input signal into a maximum signal value of the each section, the each section is multiplied into the corresponding distortion coefficient and combined together to obtain a distorted signal, where the distortion coefficients are transformed into a distortion function; a delta sigma modulation (DSM) block converting the distorted signal, fed from the first output, into a digitally modulated distorted signal; a DSM based envelope modulator converting the multiplicative inverse of the distortion function, fed from the second output, into a correction signal; a dynamic supply modulator converting the correction signal into a feeding signal; and a Class-D RF power amplifier having at least a RF input and a DC input, wherein the digitally modulated distorted signal is applied to the RF input and the feeding signal is applied to the DC input, amplifying the digitally modulated distorted signal via correcting the amplified digitally modulated distorted signal with the feeding signal generating a digitally modulated signal, having a high signal to noise ratio.

3. A method for carrying out the class-S RF transmitter for Magnetic Resonance Imaging (MRI) scanners as in claim 1, the method comprising the steps of: splitting an analog input signal into sections in equal time intervals by a Peak to Average Ratio Reduction (PARR) block having at least a first output and a second output; calculating a distortion coefficient for each section by dividing a maximum signal value of each section into a maximum signal value of the analog input signal; dividing each section into corresponding distortion coefficient; combining each divided section to obtain a distorted signal; transforming the distortion coefficients into a distortion function; converting the distorted signal, fed from the first output, into a digitally modulated distorted signal by a delta sigma modulation (DSM) block; converting a multiplicative inverse of the distortion function, fed from the second output, into a correction signal by a DSM based envelope modulator; converting the correction signal into a feeding signal by a dynamic supply modulator; amplifying the digitally modulated distorted signal by a class-D RF power amplifier which the digitally modulated distorted signal is applied to an RF input of class-D RF amplifier; and generating a digitally modulated signal having a high signal to noise ratio via correcting the amplified digitally modulated distorted signal with the feeding signal by the class-D RF power amplifier which the feeding signal is applied to a DC input of the class-D RF power amplifier.

4. A method for carrying out the class-S RF transmitter for Magnetic Resonance Imaging (MRI) scanners as in claim 2 comprising the steps of: splitting an analog input signal into sections in equal time intervals by a Peak to Average Ratio Reduction (PARR) block having at least a first output and a second output; calculating a distortion coefficient for each section by dividing a maximum signal value of the analog input signal into a maximum signal value of the each section; multiplying the each section into corresponding distortion coefficient; combining each divided section to obtain a distorted signal; transforming the distortion coefficients into a distortion function; converting the distorted signal, fed from the first output, into a digitally modulated distorted signal by a delta sigma modulation (DSM) block; converting the multiplicative inverse of the distortion function, fed from the second output, into a correction signal by a DSM based envelope modulator; converting the correction signal into a feeding signal by a dynamic supply modulator; amplifying the digitally modulated distorted signal by a class-D RF power amplifier wherein the digitally modulated distorted signal is applied to an RF input of the class-D RF amplifier; and generating a digitally modulated signal having a high signal to noise ratio via correcting the amplified digitally modulated distorted signal with the feeding signal by the class-D RF power amplifier wherein the feeding signal is applied to a DC input of the class-D RF amplifier.

Description

BRIEF DESCRIPTION OF THE DRAWINGS

(1) An exemplary embodiment of the present invention is illustrated by way of example in the accompanying drawings to be more easily understood and uses thereof will be more readily apparent when considered in view of the detailed description, in which like reference numbers indicate the same or similar elements, and the following figures in which:

(2) FIG. 1. A prior art basic block diagram of a conventional transmitter for MRI scanners.

(3) FIG. 2. A prior art basic block diagram of new generation multi-channel, all-digital RF transmitter for MRI scanners.

(4) FIG. 3. A prior art basic block diagram of DSM based Class-S RF transmitter for MRI scanners.

(5) FIG. 4. Basic block diagram of one embodiment of Class-S RF transmitter for Magnetic Resonance Imaging (MRI) scanners.

(6) FIG. 5. An exemplary illustration of a distortion function for 2 ms Sinc signal.

(7) FIG. 6. An exemplary illustration of a correction function for 2 ms Sinc signal.

(8) FIG. 7. An exemplary illustration of an analog input signal for 2 ms Sinc signal.

(9) FIG. 8. An exemplary illustration of a distorted signal (reduced peak to average amplitude variation signal) of 2 ms analog input Sinc signal.

(10) FIG. 9. An exemplary illustration of digitally modulated signal with high signal to noise ratio (SNR) of an analog input signal at the Class-D RF power amplifier.

(11) FIG. 10. An exemplary illustration of a RF signal at a band pass filter output.

(12) FIG. 11. An exemplary illustration of an envelope signal of a RF Sinc signal not applied to the Peak to Average Ratio Reduction process at a band pass filter output.

(13) FIG. 12. An exemplary illustration of an envelope signal of a RF Sinc signal applied to the Peak to Average Ratio Reduction process at a band pass filter output.

(14) FIG. 13. An exemplary illustration of a frequency spectrum of a RF Sinc signal not applied to the Peak to Average Ratio Reduction process at Class-S RF transmitter output.

(15) FIG. 14. An exemplary illustration of a frequency spectrum of a RF Sinc signal applied to the Peak to Average Ratio Reduction process at Class-S RF transmitter output.

DETAILED DESCRIPTION OF THE EMBODIMENTS

(16) The present invention is related to Class-S RF transmitter for Magnetic Resonance Imaging (MRI) scanners. The Class-S RF transmitter decreases the peak to average amplitude variation of the analog input signal. Thereby, the input signal is sampled efficiently at all amplitude values and Delta Sigma Modulation (DSM) Block performance is increased that a higher SNR and better signal linearity are acquired.

(17) In the present invention, an analog input signal (X.sub.(n)) is processed by a Peak to Average Ratio Reduction (PARR) block to diminish the difference between peak amplitudes and average amplitudes of the analog input signal (X.sub.(n)). After a distorted signal (h.sub.(n)), having low peak to average amplitude ratio, generated at the PARR block output, is processed by a delta sigma modulation (DSM) block converting the distorted signal (h.sub.(n)) into a digitally modulated distorted signal (h_dsm.sub.(n)) with high signal to noise ratio (SNR). Afterwards, the digitally modulated distorted signal (h_dsm.sub.(n)) is corrected and amplified by a Class-D RF power amplifier fed from a dynamic supply modulator by a feeding signal (env.sub.(n)) generated from a digital correction signal (z_dsm.sub.(n)). As a result, a digitally modulated signal (y.sub.(n)) with high signal to noise ratio (SNR) of the analog input signal (X.sub.(n)) is generated at the output of the Class-D RF power amplifier.

(18) In the Class-S RF transmitter for MRI scanners, an analog input signal (X.sub.(n)) is applied to a Peak to Average Ratio Reduction (PARR) block having at least a first output and a second output. In PARR block the analog input signal (X.sub.(n)) is split into sections in equal time intervals (t.sub.0). Preferably, the time interval (t.sub.0) is selected according to sampling frequency (f.sub.sw) of the PARR block. A distortion coefficient (k.sub.(m)) for each section is calculated by dividing the maximum signal value (amplitude value) of each sections into the maximum signal value of the analog input signal (X.sub.(n)). Afterwards, each section is divided into corresponding distortion coefficient (k.sub.(m)) and combined together to obtain a distorted signal (h.sub.(n)) which is the analog input signal (X.sub.(n)) peak to average amplitude ratio value of which is reduced. Dividing a section into corresponding distortion coefficient (k.sub.(m)) amplifies the each section. Technically, the maximum amplitude value of the section is equalized to the maximum amplitude value of the analog input signal (X.sub.(n)) [see FIG. 7, 8]. The combination of each amplified section is the analog input signal (X.sub.(n)) low amplitude of which is amplified.

(19) In another embodiment of the invention, the distortion coefficient (k.sub.(m)) for each section is calculated by dividing the maximum signal value of the analog input signal (X.sub.(n)) into the maximum signal value (amplitude value) of each sections. Afterwards, each section is multiplied by corresponding distortion coefficient (k.sub.(m)) and combined together to obtain distorted signal (h.sub.(n)) which is the analog input signal (X.sub.(n)) peak to average amplitude value of which is reduced. Multiplying a section into corresponding distortion coefficient (k.sub.(m)) amplifies the each section. Technically, the maximum amplitude value of the section is equalized to the maximum amplitude value of the analog input signal (X.sub.(n)) [see FIG. 7, 8]. The combination amplified sections is the analog input signal (X.sub.(n)) low amplitude of which is amplified.

(20) The distorted signal (h.sub.(n)) is applied to a delta sigma modulation (DSM) block from the first output of the PARR block. The DSM block converts the distorted signal (h.sub.(n)) into a digitally modulated distorted signal (h_dsm.sub.(n)).

(21) In the PARR block, the distortion coefficients (k.sub.(m)) are transformed into a distortion function (k.sub.(n)). Afterwards, the multiplicative inverse of the distortion function (1/k.sub.(n)) is applied to a DSM based envelope modulator from the second output of the PARR block. The DSM based envelope modulator converts the multiplicative inverse of the distortion function (1/k.sub.(n)) into a correction signal (z_dsm.sub.(n)). Thereafter, the correction signal (z_dsm.sub.(n)) applied into dynamic supply modulator. Dynamic supply modulator converts the correction signal (z_dsm.sub.(n)) into a high power (high voltage and high current) DC feeding signal (env.sub.(n)).

(22) The digitally modulated distorted signal (h_dsm.sub.(n)) is applied to RF input of a Class-D RF power amplifier running in switching mode and the feeding signal (env.sub.(n)) is applied to DC input of the Class-D RF power amplifier. The Class-D RF power amplifier amplifies and corrects the digitally modulated distorted signal (h_dsm.sub.(n)) via the feeding signal (env.sub.(n)) such that a digitally modulated signal (y.sub.(n)) with high signal to noise ratio (SNR) of the analog input signal (X.sub.(n)) is generated at the output of the Class-D RF power amplifier.

(23) Now, the generated digitally modulated signal (y.sub.(n)) can be converted into an amplified Sinc signal at the RF carrier frequency by a band pass filter. Thus, more linear Sinc signal with high efficiency is obtained at the Class-S RF transmitter output.

(24) It is illustrated that an envelope signal of a RF Sinc signal not applied to the Peak to Average Ratio Reduction process at a band pass filter output in FIG. 11 and an envelope signal of a RF Sinc signal applied to the Peak to Average Ratio Reduction process at a band pass filter output in FIG. 12 (the band width of the band pass filter at the output of the Class-S RF transmitter is 1 MHz). It is clearly seen in the figures that the low amplitude areas of the signal are recovered with a lower noise in the FIG. 12 rather than FIG. 11.

(25) It is illustrated that a frequency spectrum of a RF Sinc signal not applied to the Peak to Average Ratio Reduction process at Class-S RF transmitter output in FIG. 13 and frequency spectrum of a RF Sinc signal applied to the Peak to Average Ratio Reduction process at Class-S RF transmitter output in FIG. 14. It is clearly seen in the spectrums that the noise level of the signal in and out of the signal band is lower in the FIG. 12 rather than FIG. 11.

(26) The functional representation of the Class-S RF transmitter method is disclosed below;

(27) $\left[h\left[n\right],1/k\left[n\right]\right]=f_{\mathrm{PARR}}\left[x\left[n\right]\right]$$k\left[m\right]=\frac{\max \left(x\left[n\text{:}n+k_0\right]\right)}{\max \left(x\left[n\right]\right)},m=0,\mathrm{.Math.},\frac{N}{k_0},k_0=\frac{N}{T{f}_{\mathrm{sw}}},f_{\mathrm{sw}}=\frac{1}{t_0}$$k\left[n\right]=\mathrm{upsample}\left(k\left[m\right],k_0\right)$$f_{\mathrm{dsm}\_\mathrm{env}}=\frac{1-z^{-1}}{\left(1-z^{-1}\right)+\frac{1}{\left(1-z^{-1}\right)}+2}{\left(\frac{z}{z+1}\right)}^2$$z_{\mathrm{dsm}\left[n\right]}=f_{\mathrm{dsm}\_\mathrm{env}}.Math.\left(\frac{1}{k\left[n\right]}\right)$$\mathrm{env}\left[n\right]=z_{\mathrm{dsm}\left[n\right]}{V}_{\mathrm{dd}}$$f_{\mathrm{dsm}\_\mathrm{RF}}=\frac{1-z^{-1}}{\left(1-z^{-1}\right)+\frac{1}{\left(1-z^{-1}\right)}+2}{\left(\frac{z}{z+1}\right)}^2$$h\left[n\right]=x\left[n\right]k\left[n\right]$$\mathrm{h\_dsm}\left[n\right]=f_{\mathrm{dsm}\_\mathrm{RF}}.Math.h\left[n\right]$$y\left[n\right]=A\mathrm{h\_dsm}\left[n\right]\mathrm{env}\left[n\right]$

(28) Nomenclature x[n]: Analog input signal x[n]=x(t=nt.sub.0), n=0, . . . , N, t=0, . . . , T h[n]: Distorted signal k[n]: Distortion coefficient .sub.PAR: Peak to Average Ratio Reduction (PARR) block function A: Power amplifier gain V.sub.dd: Voltage Drain Drain T: Input signal pulse duration N: Input signal sampling number .sub.dsm_env: DSM based envelope modulator function z.sub.dsm[n]: Correction signal env[n]: Feeding signal y[n]: Digitally modulated signal (y(n)) with high signal to noise ratio (SNR) of the analog input signal (X(n)) h_dsm[n]: Digitally modulated distorted signal .sub.dsm_RF: DSM block function .sub.sw: Sampling frequency

(29) The foregoing embodiments are merely descriptions on preferred implementations of the present invention, rather than limitations to the concept and scope of the present invention. Various variations and improvements made by a person of ordinary skill in the art on the technical solutions of the present invention without departing from the design concept of the present invention shall all fall within the protection scope of the present invention. The technical contents claimed by the present invention are all recorded in the claims.