CURRENT FED HIGH-FREQUENCY ISOLATED MATRIX CONVERTER WITH THE CORRESPONDING MODULATION AND CONTROL SCHEMES

Abstract

A current fed high-frequency isolated matrix converter and the corresponding modulation and control schemes are provided. The converter includes a current source full-bridge converter, a high-frequency transformer, a matrix converter, and a three-phase filter. An optimized space vector modulation solution is used for controlling the converter, and by comparing magnitudes of three-phase filter capacitor voltages to determine an action sequence of space vectors, switch tubes are turned on at zero voltage. A current source full-bridge circuit adopts a commutation strategy of a secondary clamping, and by calculating a leakage inductive current commutation time, full-bridge switch tubes are turned off at zero current to achieve safe and reliable commutation, and having advantages of a low system loss, a high efficiency, and a high power density.

Claims

1. A current source input high-frequency isolation matrix converter, comprising: a current source full-bridge converter having an input DC bus connected to a DC side current source, a high-frequency transformer having a primary coil connected to an output end of the current source full-bridge converter, a matrix converter having a DC bus connected to a secondary coil of the high-frequency transformer, and a three-phase filter circuit, wherein a capacitor in each phase filter circuit is connected in parallel between a midpoint of a corresponding phase bridge arm of the matrix converter and a reference potential point, and an output end of the each phase filter circuit is connected to an AC side, wherein an action sequence of current vectors of the matrix converter is determined according to a line voltage loaded on a filter capacitor, and the current source input high-frequency isolation matrix converter is subjected to a positive half-cycle zero vector action stage, a first active vector action stage, a second active vector action stage, a current source full-bridge converter commutation stage, a current source full-bridge converter freewheeling stage, and a negative half-cycle zero vector action stage in turn under the action sequence of the current vectors.

2. A method for controlling the current source input high-frequency isolation matrix converter according to claim 1, wherein the current source full-bridge converter comprises: a first bridge arm formed by a first switch tube and a second switch tube connected in series, and a second bridge arm formed by a third switch tube and a fourth switch tube connected in series, and the matrix converter comprises: an a-phase bridge arm formed by a first bidirectional switch tube and a fourth bidirectional switch tube connected in series, a b-phase bridge arm formed by a third bidirectional switch tube and a sixth bidirectional switch tube connected in series, and a c-phase bridge arm formed by a fifth bidirectional switch tube and a second bidirectional switch tube connected in series; and three current vectors acting on the matrix converter in a positive half cycle of a switch are a zero vector I.sub.7, a first active vector I.sub.1+, and a second active vector I.sub.2+, corresponding input voltages of the matrix converter are U.sub.0, U.sub.1, and U.sub.2, after line voltages on adjacent two-phase capacitors are compared, and when an action sequence of the three current vectors is determined to be I.sub.7−>I.sub.1+−>I.sub.2+, U.sub.2>U.sub.1>U.sub.0, and a control process of the current source input high-frequency isolation matrix converter in the positive half cycle of the switch is as follows: state 1: the positive half-cycle zero vector action stage at a beginning of a switch cycle, the zero vector I.sub.7 acts on the matrix converter, the first bidirectional switch and the fourth bidirectional switch in the matrix converter are turned on, and the first switch tube and the fourth switch in the current source full-bridge converter are turned on; state 2: the first active vector action stage after a zero vector action time has expired, the first active vector I.sub.1+ acts on the matrix converter, the first switch tube and the fourth switch tube in the current source full-bridge converter maintain an ON state, a phase voltage on an ab-phase capacitor is greater than 0, a secondary current of the high-frequency transformer charges an output capacitor of the sixth bidirectional switch tube, the sixth bidirectional switch tube is turned on at zero voltage, the fourth bidirectional switch tube is turned off, a secondary voltage of the high-frequency transformer is equal to a line voltage on the ab-phase capacitor, and an energy is fed from a DC side to the AC side; state 3: the second active vector action stage after an action time of the first active vector I.sub.1+ has expired, the second active vector I.sub.2+ acts on the matrix converter, the first switch tube and the fourth switch tube in the current source full-bridge converter maintain the ON state, a line voltage on an ac-phase capacitor is greater than the line voltage on the ab-phase capacitor, the secondary current of the high-frequency transformer charges an output capacitor of the second bidirectional switch, the second bidirectional switch is turned on at zero voltage, the sixth bidirectional switch is turned off, the secondary voltage of the high-frequency transformer is equal to the line voltage on the ac-phase capacitor, and the energy is fed from the DC side to the AC side; state 4: the current source full-bridge converter commutation stage in the matrix converter, the first bidirectional switch tube and the second bidirectional switch tube maintain the ON state, the first, second, third, and fourth switches of the current source full-bridge converter are overlapped and turned on, and the second switch tube and the third switch tube are turned on at zero current; state 5: the current source full-bridge converter freewheeling stage after an overlapped ON time of the first, second, third, and fourth switches of the current source full-bridge converter has expired, the second bidirectional switch tube in the matrix converter is turned off, the fourth bidirectional switch tube is turned on at zero voltage, a secondary voltage of the current source full-bridge converter is zero, anti-parallel diodes of the first switch tube and the fourth switch tube are freewheeling, and the first switch tube and the fourth switch tube are turned off at zero current; and state 6: the negative half-cycle zero vector action stage after the first switch tube and the fourth switch tube are turned off at zero current, the zero vector I.sub.7 acts on the matrix converter, the first bidirectional switch and the fourth bidirectional switch tube in the matrix converter maintain the ON state, and the second switch tube and the third switch tube in the current source full-bridge converter maintain the ON state.

3. The method according to claim 2, wherein action times of the three current vectors of the matrix converter are corrected according to the overlapped ON time of the first, second, third, and fourth switches of the current source full-bridge converter to obtain corrected action times.

4. The method according to claim 3, wherein the corrected action times of the three current vectors of the matrix converter are: ${\begin{matrix} T_{1} = T_{s} m_{a} \sin (\frac{π}{6} - θ_{i}) \\ T_{2} = T_{s} m_{a} \sin (\frac{π}{6} + θ_{i}) + 2 T_{d}, \\ T_{0} = T_{s} - T_{1} - T_{2} \end{matrix}$ wherein T.sub.1, T.sub.2, and T.sub.0 are the action times of the first active vector I.sub.1+, the second active vector I.sub.2+, and the zero vector I.sub.7, respectively, m.sub.a and θ.sub.i are a modulation ratio and an angle of space vector modulation, T.sub.s is a switch cycle, and T.sub.d is the overlapped ON time of the first, second, third, and fourth switches of the current source full-bridge converter.

5. The method according to claim 4, wherein the overlapped ON time of the first, second, third, and fourth switches of the current source full-bridge converter is
T.sub.d=2i.sub.LmL.sub.1n.sub.s/u.sub.acn.sub.p, wherein T.sub.d is the overlapped ON time of the first, second, third, and fourth switches of the current source full-bridge converter, i.sub.Lm is a DC bus current of the current source full-bridge converter, L.sub.1 is a leakage inductance of the high-frequency transformer, n.sub.p/n.sub.s is a turn ratio of the high-frequency transformer, and u.sub.ac is the line voltage on the ac-phase capacitor.

6. A control system of the current source input high-frequency isolation matrix converter according to claim 1, comprising: a PLL having an input end connected to line voltages on adjacent two-phase capacitors, and outputting a grid frequency ω.sub.g, a grid phase θ.sub.g, and a dq-axis component of a voltage of the filter capacitor; a low-pass filter having an input end connected to the dq-axis component of the voltage of the filter capacitor and the grid frequency, and outputting a steady-state current of the filter capacitor; a current given-value correction module having an input end connected to a given current value and an actual current value of the input DC bus of the current source full-bridge converter and a d-axis component of the steady-state current of the filter capacitor, wherein an error between the given current value and the actual current value of the input DC bus of the current source full-bridge converter is processed by a PI and then accumulates the d-axis component of the steady-state current of the filter capacitor, and a final current given-value is outputted; a coordinate transformation module configured to perform a coordinate transformation on the final current given-value, and output a given-value of a DC current and a trigger delay angle; and a space vector modulation module having an input end connected to the given-value of the DC current and the trigger delay angle, and configured to calculate a modulation ratio and a modulation angle, and then output a switching pulse of the matrix converter.

7. The control system according to claim 6, wherein the control system further comprises a selector and an overlapped ON time calculation module, wherein the selector is configured to select a maximum value from the line voltages on the adjacent two-phase capacitors and output the maximum value, and the overlapped ON time calculation module is configured to calculate an overlapped ON time of switches of the current source full-bridge converter according to the maximum value outputted by the selector, a current of the input DC bus of the current source full-bridge converter, and a leakage inductance of the high-frequency transformer, and the space vector modulation module is configured to correct action times of three current vectors of the matrix converter according to a calculation result outputted by the overlapped ON time calculation module.

8. The current source input high-frequency isolation matrix converter according to claim 1, wherein the converter is suitable for application scenarios of a sine wave power supply.

9. A driving system of a fuel cell hybrid electric motor, comprising the current source input high-frequency matrix converter according to claim 1, wherein a DC converter connected between a current source and the input DC bus of the current source full-bridge converter, an output end of the three-phase filter circuit is connected to a three-phase motor.

10. The driving system according to claim 9, wherein a modulation ratio is set to a fixed value, a phase of a voltage of a three-phase filter capacitor is detected by using an encoder, and a current inputted to the DC bus of the current source full-bridge converter is adjusted by controlling the DC converter.

Description

BRIEF DESCRIPTION OF THE DRAWINGS

[0035] FIG. 1 is a topological diagram of a main circuit of a current source input high-frequency matrix converter disclosed in this application.

[0036] FIG. 2A and FIG. 2B are current space vector diagrams of a positive half cycle and a negative half cycle of a matrix converter.

[0037] FIG. 3 is a flowchart of sorting current vectors in a positive half cycle of a first sector.

[0038] FIG. 4A to FIG. 4F are current flow path diagrams when a converter is in State 1, State 2, State 3, State 4, State 5, and State 6 during the first half of a switch cycle.

[0039] FIG. 5 is a flowchart of switching a zero vector I.sub.7 to an active vector I.sub.1+.

[0040] FIG. 6 is a key oscillogram in a switch cycle.

[0041] FIG. 7 is a system block diagram of a control system of a current source input high-frequency isolation matrix converter disclosed in this application.

[0042] FIG. 8 is a decoupling circuit diagram of a current source input high-frequency matrix converter disclosed in this application.

[0043] FIG. 9 is a circuit diagram of a driving system of a current input motor according to a specific embodiment.

[0044] FIG. 10 is a comparison diagram of input voltages and currents of a matrix converter under different angles.

[0045] FIG. 11 is an oscillogram of a steady-state voltage and current of a matrix converter.

[0046] Illustration of reference numerals: 1.1, storage battery, 1.2, bus inductor, 1.3, current source full-bridge converter, 1.4, high-frequency transformer, 1.5, matrix converter, 1.6, three-phase filter circuit, and 1.7, three-phase load.

DETAILED DESCRIPTION OF THE EMBODIMENTS

[0047] The technical solution of the present invention will be described in detail with reference to the accompanying drawings.

[0048] The current source input high-frequency isolation matrix converter disclosed in this application is shown in FIG. 1. A DC side adopts a current source input converter, and a grid side adopts a direct matrix converter. The current source input converter transmits energy to a single-stage matrix converter through a high-frequency transformer. The current source full-bridge converter 1.3 is a full-bridge converter formed by a first switch tube S.sub.1, a second switch tube S.sub.2, a third switch tube S.sub.3, and a fourth switch tube S.sub.4. The matrix converter 1.5 includes: a first bidirectional switch tube in which a switch tube S.sub.21 and a switch tube S.sub.11 are connected to a common source, a second bidirectional switch tube in which a switch tube S.sub.22 and a switch tube S.sub.12 are connected to a common source, a third bidirectional switch tube in which a switch tube S.sub.23 and a switch tube S.sub.13 are connected to a common source, a fourth bidirectional switch tube in which a switch tube S.sub.24 and a switch tube S.sub.14 are connected to a common source, a fifth bidirectional switch tube in which a switch tube S.sub.25 and a switch tube S.sub.15 are connected to a common source, a sixth bidirectional switch tube in which a switch tube S.sub.26 and a switch tube S.sub.16 are connected to a common source, a midpoint of a bridge arm formed by the first bidirectional switch tube and the fourth bidirectional switch tube connected in series is denoted as a, a midpoint of a bridge arm formed by the third bidirectional switch tube and the sixth bidirectional switch tube connected in series is denoted as b, and a midpoint of a bridge arm formed by the fifth bidirectional switch tube and the second bidirectional switch tube connected in series is denoted as c. A three-phase filter circuit 1.6 includes three single-phase filter circuits, each single-phase filter circuit is an LC series circuit, capacitors of the three single-phase filter circuits are connected in parallel to a point O, and inductors of the three single-phase filter circuits are connected to a three-phase load 1.7. A bus inductor 1.2 is connected in series to an input DC bus of the current source full-bridge converter 1.3, a storage battery 1.1 is connected in series to the bus inductor 1.2, and the bus inductor 1.2 provides a stable DC bus current for the full-bridge converter. A primary coil of a high-frequency transformer 1.4 is connected to an output side formed by the midpoint of the two bridge arms of the current source full-bridge converter 1.3, and a DC bus of the matrix converter 1.5 is connected to a secondary coil of the high-frequency transformer 1.4. The midpoints of the three bridge arms of the matrix converter 1.5 are respectively connected to connection points of a capacitor and an inductor in each phase filter circuit.

[0049] The current source input matrix converter shown in 1 may be equivalently decoupled as two three-phase current source converters connected in parallel as shown in 8; therefore, a current space vector modulation method can be applied to the current source input matrix converter, and changing an action sequence of current vectors can cause input voltages of the converter to be ascending, thereby realizing the soft switching of all switch tubes, further reducing the loss of the converter, reducing the mass and volume of an EMI filter, and increasing the power density of the system. The commutation of the primary current source full-bridge converter takes up part of action time of the active vector of the matrix converter, which leads to an increase in the system output current harmonics. Therefore, it is necessary to compensate the vector action time to reduce the output current harmonics of the converter and reduce the harmonic losses.

[0050] As shown in FIG. 2A and FIG. 2B, one switch cycle of the matrix converter is divided into positive and negative half cycles with switching states differing by 180°. In order to simplify the analysis, only a mode of the first half cycle is analyzed. Taking a sector I as an example, three current vectors acting on the matrix converter 1.5 in the half switch cycle are I.sub.7, I.sub.1+, and I.sub.2+, corresponding input voltages of the current source full-bridge converter are 0, U.sub.1, and U.sub.2, and input voltages of converter are caused to be ascending by changing the action sequence of current vectors. The vector sorting method is shown in FIG. 3. It is assumed here that 0<U.sub.1<U.sub.2, and according to FIG. 3, the action sequence of the current vectors in the half cycle is I.sub.7, I.sub.1+, and I.sub.2+. A modulation process of the matrix converter in the half switch cycle is subjected to 6 states, where current circulation paths in 6 states are shown in FIGS. 4A-4F, and a key oscillogram in a switch cycle is shown in FIG. 6.

1) State 1: Matrix Converter Zero Vector Function

[0051] At the beginning of the switch cycle, a current vector corresponding to the matrix converter 1.5 is the zero vector I.sub.7. At this time, the matrix converter switch tubes S.sub.21, S.sub.11, S.sub.24, and S.sub.14 are turned on, and the current source full-bridge converter switch tubes S.sub.1 and S.sub.4 are turned on. At this time, it is in an inductive energy storage stage, and there is no energy flow between the storage battery and the grid. An equivalent circuit is shown in FIG. 4A. Waveforms of three-phase capacitor currents i.sub.wa, i.sub.wb, and i.sub.wc, a bus current i.sub.s and a switch tube control signal of the current source full-bridge converter, and primary and secondary voltages u.sub.p and u.sub.s of the high-frequency transformer may be obtained with reference to the oscillogram during the time period [t.sub.0, t.sub.1] as shown in FIG. 6.

2) State 2: Matrix Converter Active Vector Function

[0052] After the zero vector action time has expired, the first active vector I.sub.1+ of the matrix converter starts to work. The primary bus current of the transformer flows through the switch tubes S.sub.1 and S.sub.4, and the secondary current of the transformer flows through the switch tubes S.sub.21, S.sub.11, S.sub.26, and S.sub.16. Since the capacitor voltage u.sub.ab is greater than zero, the transformer current charges output capacitors of S.sub.16 and S.sub.26, S.sub.16 and S.sub.26 are turned on at zero voltage, the secondary voltage of the transformer is equal to u.sub.ab, and the power is fed from the storage battery to the grid. An equivalent circuit is shown in FIG. 4B. Waveforms of three-phase capacitor currents i.sub.wa, i.sub.wb, and i.sub.wc, a bus current i.sub.s and a switch tube control signal of the current source full-bridge converter, and primary and secondary voltages u.sub.p and u.sub.s of the high-frequency transformer may be obtained with reference to the oscillogram during the time period [t.sub.1, t.sub.2] as shown in FIG. 6.

3) State 3: Matrix Converter Active Vector Function

[0053] After an action time of the active vector I.sub.1+ of the matrix converter has expired, the second active vector I.sub.2+ of the matrix converter starts to work. The primary bus current of the transformer flows through the switch tubes S.sub.1 and S.sub.4, and the secondary current of the transformer flows through the switch tubes S.sub.21, S.sub.11, S.sub.22, and S.sub.12. Since the capacitor voltage u.sub.ac is greater than u.sub.ab, the transformer current charges output capacitors of S.sub.12 and S.sub.22, S.sub.12 and S.sub.22 are turned on at zero voltage, the secondary voltage of the transformer is equal to u.sub.ac, and the power is fed from the storage battery to the grid. An equivalent circuit is shown in FIG. 4C. Waveforms of three-phase capacitor currents i.sub.wa, i.sub.wb, and i.sub.wc, a bus current i.sub.s and a switch tube control signal of the current source full-bridge converter, and primary and secondary voltages u.sub.p and u.sub.s of the high-frequency transformer may be obtained with reference to the oscillogram during the time period [t.sub.2, t.sub.3] as shown in FIG. 6.

4) State 4: Current Source Full-Bridge Converter Commutation

[0054] All switch tubes of the current source full-bridge converter are turned on and enter an overlapped ON area of the primary switch tubes. The bus inductor limits a current change rate, and therefore, the switch tubes S.sub.2 and S.sub.3 are turned on at zero current. A secondary voltage is mapped to the primary side of the transformer, a leakage inductive current is decreased linearly, currents of the switch tubes S.sub.2 and S.sub.3 are increased linearly, and currents of the switch tubes S.sub.1 and S.sub.4 are decreased linearly. The overlapped ON time T.sub.d of the current source full-bridge converter can be calculated by Formula (1), and for reliable commutation, the time of T.sub.d is appropriately increased. The sum of output currents in the overlapped area is zero, and therefore, in order to reduce the output current harmonics of the converter, it is necessary to compensate the action time of the vectors of the matrix converter by using Formula (2). i.sub.Lm, L.sub.1, n.sub.p/n.sub.s, and u.sub.ac are bus current, transformer leakage inductance, transformer turn ratio, and ac-phase line voltage of an output capacitor, respectively. T.sub.1, T.sub.2, and T.sub.0 are the action times of vectors I.sub.1+, I.sub.2+, and I.sub.7, respectively, m.sub.a and θ.sub.i are the modulation ratio and the angle of space vector modulation, respectively, and T.sub.s is a switch cycle. An equivalent circuit of the current source full-bridge converter commutation stage is shown in FIG. 4D. Waveforms of three-phase capacitor currents i.sub.wa, i.sub.wb, and i.sub.wc, a bus current i.sub.s and a switch tube control signal of the current source full-bridge converter, and primary and secondary voltages u.sub.p and u.sub.s of the high-frequency transformer may be obtained with reference to the oscillogram during the time period [t.sub.3, t.sub.4] as shown in FIG. 6.

[00002] $\begin{matrix} T_{d} = 2 i_{Lm} L_{1} n_{s} / u_{ac} n_{p}, & (1) \end{matrix}$ $\begin{matrix} {\begin{matrix} T_{1} = T_{s} m_{a} \sin (\frac{π}{6} - θ_{i}) \\ T_{2} = T_{s} m_{a} \sin (\frac{π}{6} + θ_{i}) + 2 T_{d} \\ T_{0} = T_{s} - T_{1} - T_{2} \end{matrix} . & (2) \end{matrix}$

5) State 5: Current Source Full-Bridge Converter Freewheeling

[0055] After the overlapped ON time T.sub.d of the current source full-bridge converter has expired, the matrix converter switch tubes S.sub.12 and S.sub.22 are turned off, and S.sub.14 and S.sub.24 are turned on at zero voltage. The secondary voltage of the transformer is equal to zero, and no power is transmitted at this time. Anti-parallel diodes of the current source full-bridge converter switch tubes S.sub.1 and S.sub.4 are freewheeling, S.sub.1 and S.sub.4 are turned off at zero current, and an equivalent circuit is shown in FIG. 4E. Waveforms of three-phase capacitor currents i.sub.wa, i.sub.wb, and i.sub.wc, a bus current i.sub.s and a switch tube control signal of the current source full-bridge converter, and primary and secondary voltages u.sub.p and u.sub.s of the high-frequency transformer may be obtained with reference to the oscillogram during the time period [t.sub.4, t.sub.5] as shown in FIG. 6.

6) State 6: Inverter Switch Tube Being Turned On

[0056] Similar to State 1, the current vector corresponding to the matrix converter 1.5 is the zero vector I.sub.7. At this time, the matrix converter switch tubes S.sub.21, S.sub.11, S.sub.24, and S.sub.14 are turned on, and the current source full-bridge converter switch tubes S.sub.2 and S.sub.3 are turned on. At this time, it is in an inductive energy storage stage, and there is no energy flow between the storage battery and the grid. An equivalent circuit is shown in FIG. 4F. Waveforms of three-phase capacitor currents i.sub.wa, i.sub.wb, and i.sub.wc, a bus current i.sub.s and a switch tube control signal of the current source full-bridge converter, and primary and secondary voltages u.sub.p and u.sub.s of the high-frequency transformer may be obtained with reference to the oscillogram during the time period [t.sub.5, t.sub.6] as shown in FIG. 6.

[0057] The process is as follows: the commutation method of the matrix converter of this application is explained with reference to FIG. 5, taking the zero vector I.sub.7 switching to the active vector I.sub.1+ as an example, first, the converter is in the zero vector state, and the switch tubes S.sub.21, S.sub.11, S.sub.24, and S.sub.14 are turned on, where the switch tubes S.sub.21 and S.sub.24 are turned on forwardly, the switch tubes S.sub.11 and S.sub.14 are in a synchronous rectification state, and an output current of the matrix converter is zero. The entire commutation process includes the following four steps:

[0058] The first step of commutation: the switch tube S.sub.14 is turned off, and the current is commutated from a channel of S.sub.14 to a body diode of S.sub.14.

[0059] The second step of commutation: the switch tube S.sub.26 is turned on, and the current flows through a channel of S.sub.26 and a body diode of S.sub.16.

[0060] The third step of commutation: the switch tube S.sub.24 is turned off, and the output current of the matrix converter is equal to i.sub.s.

[0061] The fourth step of commutation: the switch tube S.sub.16 is turned on, and the current is commutated from the body diode of S.sub.16 to the channel of S.sub.16, and S.sub.16 is in the synchronous rectification state. For the current source input high-frequency matrix converter shown in FIG. 1, this application further proposes a control system shown in FIG. 7, which can be implemented by a DSP, and a control logic of the control system is as follows:

[0062] 1) After a capacitor voltage u.sub.abc of a filter capacitor passes through a phase-locked loop, a frequency ω.sub.g and a phase θ.sub.g of a power grid are obtained, and a dq-axis component u.sub.gdq of the filter capacitor voltage is obtained through coordinate transformation.

[0063] 2) The dq-axis component u.sub.dq of the capacitor voltage of the filter capacitor passes through a low-pass filter to obtain a steady-state component of the capacitor voltage, and steady-state currents i.sub.gcd and i.sub.gcq of the filter capacitor are calculated by Formula 3.

[00003] $\begin{matrix} {\begin{matrix} i_{\gcd} = - ω_{g} u_{q} C_{f} \\ i_{gcq} = ω_{g} u_{d} C_{f} \end{matrix} . & (3) \end{matrix}$

[0064] 3) An error between a given bus current I.sub.dc_ref and an actual current i.sub.Lm are subjected to a PI controller to obtain a given d-axis current i.sub.gd_ref. In order to obtain a unit power factor, a given system reactive power Q.sub.g_ref is zero, and a given q-axis current i.sub.gq_ref is zero.

[0065] 4) Given d-axis and q-axis currents i.sub.gd_ref and i.sub.gd_ref compensate the steady-state currents i.sub.gcd and i.sub.gcq of the capacitor to obtain a final given current, and a Cartesian coordinate system is converted to a polar coordinate system to obtain a given DC current i.sub.dci and a trigger delay angle α;

[0066] 5) The given DC current i.sub.dci is divided with the actual current value i.sub.Lm to obtain a modulation ratio m.sub.a of the space vector modulation, the delay angle and a grid phase angle θ.sub.g may be added to obtain a modulation angle θ.sub.i, and twelve switching pulses of the matrix converter are generated by using the modulation ratio and the angle;

[0067] 6) A current overlapped time of the current source full-bridge converter may be obtained according to Formula 1, and then an output pulse of the current source full-bridge converter may be generated.

[0068] Compared with the conventional current source space vector modulation method, the space vector modulation solution used in this application not only calculates an action time of each current vector, but also adjusts an action sequence of the current vectors according to magnitudes of voltages outputted by a three-phase capacitor to achieve soft switching of all switch tubes.

[0069] As shown in FIG. 10, at each modulation angle of sector I, the input voltage u.sub.s of the matrix converter may be ascending, that is, all the switch tubes of the matrix converter are turned on at zero voltage at this time, and the soft switching helps reduce the rate of voltage change of the system, suppress the electromagnetic interference of the system, and reduce the volume and mass of the system EMI filter. As can be seen from FIG. 11, the current of the bus inductor and the current of the three-phase grid are constant, and the constant bus current makes the high-frequency transformer current a square wave, which helps extend the service life of a DC power supply, and using the bus inductor to replace the bus electrolytic capacitor helps enhance the reliability of the system.

[0070] As can be seen from FIG. 8, the current source input high-frequency matrix converter disclosed in this application can be equivalently decoupled into two current source fed three-phase converters connected in parallel, so the current source input matrix converter is suitable for application scenarios of current source three-phase converters, that is, application scenarios that require sine wave power supply, and have advantages of desirable output waveform quality, low electromagnetic interference, and strong short-circuit resistance of the current source three-phase inverters. For example, the current source input high-frequency matrix converter disclosed in this application is used for a driving system of a fuel cell hybrid motor. As shown in FIG. 9, a DC/DC converter is connected in series between a fuel cell and an inductor to adjust an output voltage of a lithium battery, and then control a current of a bus inductor. Compared with a grid-connected current input matrix converter, a modulation degree is used for controlling the bus current. When the current source input matrix converter is applied to the field of hybrid electric motor driving, a modulation ratio of the matrix converter is kept at a fixed unit value, a bus current is controlled by a DC converter of the lithium battery, and phase tracking of a voltage of a three-phase capacitor no longer uses a phase-locked loop, but is realized by encoder detection. When the motor is in a braking state, the direction of the bus current does not change, an average output voltage of the DC converter is a negative value, and motor energy can be fed back to the lithium battery through the DC converter.

[0071] The foregoing embodiments are merely preferred embodiments of the present invention, but the embodiments are not intended to limit the scope of implementation of the present invention. A person skilled in the art may make various changes and modifications without departing from the spirit and scope of the present invention. Therefore, the protection scope of the present invention should be subject to the claims.

CURRENT FED HIGH-FREQUENCY ISOLATED MATRIX CONVERTER WITH THE CORRESPONDING MODULATION AND CONTROL SCHEMES

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H02M5/297

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H02M7/4807

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H02M1/0058

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H02M7/53876

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H02M5/297

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H02M3/335

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Abstract

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Description