Control method for starting a synchronous electric motor

Abstract

A control method implemented in a variable speed drive for starting a synchronous electric motor, said method including the application, as input, of a reference speed according to a predefined speed profile, the determination of a reference position based on the reference speed that is applied as input, the determination of a voltage in a rotating frame of reference, based on the reference speed that is applied as input, the determination of control voltages to be applied to each output phase depending, on the one hand, on the determined reference position and, on the other hand, on said voltage determined in the rotating frame of reference, and the application of the control voltages to each output phase to obtain an alignment of the position of the rotor of said motor with the reference position.

Claims

1. A control method implemented in a variable speed drive for starting a synchronous electric motor (M) equipped with a rotor and connected via output phases to said variable speed drive, said method comprising: applying, as input, a reference motor speed (s) according to a predefined speed profile, said speed profile being at least continuous and comprising a zero initial value, at least a non-zero value in order to cause the rotor of said motor to rotate and a zero final value; determining a reference position (s) based on the reference speed that is applied as input; determining a voltage (Vdq) in a frame of reference rotating at the speed of the electric motor, based on the reference speed that is applied as input; determining control voltages (Va, Vb, Vc) to be applied to each output phase depending on the determined reference position and on said voltage determined in the rotating frame of reference; and applying the control voltages (Va, Vb, Vc) to each output phase to obtain an alignment of the position of the rotor of said motor with the reference position (s), wherein the non-zero value of the predefined speed profile includes a maximum speed value that is determined depending on at least one of a number of turns to be applied to the synchronous electric motor and a predetermined duration of alignment.

2. The control method according to claim 1, wherein the determining the voltage in the rotating frame of reference is carried out with control of the current and includes: measuring the currents (ia, ib, ic) flowing through the output phases; transforming these currents measured in the three output phases into a measured flux current and a measured torque current; determining a reference flux current (idref) and a reference torque current (iqref) based on the reference speed injected as input; and determining the voltage in the rotating frame of reference by virtue of a proportional-integral controller that receives, as input, the measured flux current (id), the measured torque current (iq), the reference flux current (idref) and the reference torque current (iqref).

3. The control method according to claim 1, wherein determining the voltage in the rotating frame of reference is carried out without control of the current by applying a U/F (volts per hertz) type control rule.

4. A control system arranged in a variable speed drive for starting a synchronous electric motor (M) equipped with a rotor and connected via output phases to said variable speed drive, said system comprising: processing circuitry configured to: apply, as input, a reference motor speed (s) according to a predefined speed profile, said speed profile being at least continuous and comprising a zero initial value, at least a non-zero value in order to cause the rotor of said motor to rotate and a zero final value, determine a reference position (s) based on the reference speed that is applied as input, determine a voltage (Vdq) in a frame of reference rotating at the speed of the electric motor, based on the reference speed that is applied as input, determine control voltages (Va, Vb, Vc) to be applied to each output phase depending on the determined reference position and, on said voltage determined in the rotating frame of reference, and apply the control voltages (Va, Vb, Vc) to each output phase to obtain an alignment of the position of the rotor of said motor with the reference position (s), wherein the non-zero value of the predefined speed profile includes a maximum speed value that is determined depending on at least one of a number of turns to be applied to the synchronous electric motor and a predetermined duration of alignment.

5. The control system according to claim 4, wherein the processing circuitry is further configured to determine the voltage in the rotating frame of reference with control of the current by being configured to measure the currents (ia, ib, ic) flowing through the output phases, transform the currents measured in the three output phases into a measured flux current and a measured torque current, determine a reference flux current (idref) and a reference torque current (iqref) based on the reference speed injected as input, and determine the voltage in the rotating frame of reference by virtue of a proportional-integral controller that receives, as input, the measured flux current (id), the measured torque current (iq), the reference flux current (idref) and the reference torque current (iqref).

6. The control system according to claim 4, wherein the processing circuitry is further configured to determine the voltage in the rotating frame of reference without control of the current by applying a U/F (volts per hertz) type control rule.

7. The control system according to claim 4, wherein the non-zero value of the predefined speed profile includes a maximum speed value that is determined depending on both the number of turns to be applied to the synchronous electric motor and the predetermined duration of alignment.

Description

BRIEF DESCRIPTION OF THE FIGURES

(1) Other features and advantages will appear in the following detailed description given in conjunction with the appended drawings in which:

(2) FIG. 1 shows the diagram of a variable speed drive that is connected to a synchronous electric motor;

(3) FIG. 2 is a diagrammatic representation of the overview of the control method of the invention;

(4) FIG. 3 illustrates the vectorial representation of a synchronous motor in a rotating frame of reference;

(5) FIGS. 4A to 4D illustrate simulation results for a first operating situation;

(6) FIGS. 5A to 5D illustrate simulation results for a second operating situation;

(7) FIGS. 6A to 6D illustrate simulation results for a third operating situation.

DETAILED DESCRIPTION OF AT LEAST ONE EMBODIMENT

(8) The control method of the invention is implemented in a variable speed drive for starting a synchronous electric motor. The control method is applicable to any synchronous electric motor, e.g. of variable reluctance type, non-salient or salient permanent magnet type, etc.

(9) Referring to FIG. 1, the variable speed drive is connected upstream to an electrical distribution network N by three input phases R, S, T. In a known manner, the variable speed drive comprises an input stage composed of a rectifier REC, e.g. of diode bridge type, that is arranged so as to rectify the AC voltage provided by the network N. The variable speed drive also comprises a DC power supply bus connected to the rectifier and comprising two power supply lines that are connected to one another by one or more bus capacitors. The variable speed drive also comprises an output stage composed of an inverter INV that receives a DC voltage provided by the DC power supply bus and controlled so as to provide variable voltages as output to the synchronous electric motor M, via three output phases a, b, c.

(10) In a known manner, the control unit UC of the variable speed drive implements a main control law L for controlling the inverter and determining the output voltages that are required for the operation of the electric motor M (block B1 in FIG. 2). Conventionally, this main control law L comprises, as input, a reference speed ref based on which it determines a reference torque current (not shown). It also receives, as input, a reference flux current Idref. Based on the reference torque current and the reference flux current and measurements or estimations of the flux current Id and the torque current Iq, it determines reference voltages Vdref, Vqref based on which the single voltages Va, Vb, Vc to be applied to each output phase (block B2) are determined.

(11) On starting the synchronous electric motor M, the position of the rotor is not known to the control unit UC of the variable speed drive, which prevents implementation of the main control law L. On starting the synchronous electric motor M, according to the invention, a specific sequence is implemented in order to align the rotor with a known position. The control method of the invention allows a sequence for starting (ST, FIG. 2) the rotation of the motor to be created. For starting the synchronous electric motor, the control method of the invention thus replaces the main control law L.

(12) Referring to FIG. 2, the control method of the invention, implemented in the control unit UC for starting the synchronous electric motor, consists in applying, as input, a reference speed s that follows a predefined profile generated by a specific module (block B3). In the context of the invention, the predefined profile responds to certain constraints, namely the following: the curve of the profile follows a continuous function of a class that is at least equivalent to C0; the initial reference speed s is zero; the reference speed s takes a value that is at least non-zero in order to cause the rotor to rotate; the final reference speed is zero.

(13) Advantageously, the predefined profile comprises a zero initial value, follows an increasing slope up to a maximum value, then a decreasing slope towards a zero final value. The maximum speed value is determined depending on the number of turns to be applied to the electric motor and the desired duration of alignment. The maximum frequency that corresponds to the maximum value of the speed applied to the motor thus follows the following relationship:

(14) $F_{\mathrm{DcMax}}=\frac{2\mathrm{RndNLD}}{T_{\mathrm{pw}}+T_{\mathrm{mw}}}$
In which: RndNLD is the number of turns; (T.sub.pw+T.sub.mw) is the total duration for the alignment; F.sub.DcMax is the maximum rotational frequency in Hz; the relationship between the maximum speed .sub.sMax and the maximum frequency F.sub.DcMax is: .sub.sMax=2F.sub.DcMax

(15) Referring to FIG. 2, based on the reference speed that follows the predefined profile described above, the control method of the invention determines: a reference position s (block B4) that the actual position of the rotor must approach. The reference position s corresponds to the integral of the reference speed s. The expression for the reference frequency f.sub.s is:

(16) $f_s\left(t\right)=\{\begin{array}{cc}{F}_{\mathrm{DcMax}}\left(3{\left(\frac{t}{T_{\mathrm{pw}}}\right)}^2-2{\left(\frac{t}{T_{\mathrm{pw}}}\right)}^3\right)& \mathrm{if}t<T_{\mathrm{pw}}\\ F_{\mathrm{DcMax}}\left(1-3{\left(\frac{t-T_{\mathrm{pw}}}{T_{\mathrm{mw}}}\right)}^2+2{\left(\frac{t-T_{\mathrm{pw}}}{T_{\mathrm{mw}}}\right)}^3\right)& \mathrm{if}{T}_{\mathrm{pw}}t{T}_{\mathrm{pw}}+T_{\mathrm{mw}}\\ 0& \mathrm{otherwise}\end{array}$ where the reference frequency fs is linked to the reference speed by .sub.s=2f.sub.s; FDcMax is the maximum value of the reference frequency; T.sub.pw is the time taken for the frequency to rise from zero to FDcMax; T.sub.mw is the time taken for the frequency to fall from FDcMax to zero; t is the duration from the start of the alignment sequence. The reference position is obtained via the integral of the reference frequency as follows:
.sub.s=.sub.0.sup.t2f.sub.s(u)du The voltage Vdq (block B5) to be applied to the motor is determined with or without control of the current.

(17) Referring to FIG. 2, determining the torque voltage and the flux voltage with control of the current consists in: measuring the currents ia, ib, is flowing through the output phases; transforming (block B6) these currents measured in the three output phases into a flux current and a torque current, by virtue of Park's transformation; determining (block B5) a reference flux current idref and a reference torque current iqref based on the reference speed injected as input and which follows the above predefined profile; determining (block B5) the voltage Vdq in the rotating frame of reference d, q by virtue of a proportional-integral controller that receives, as input, the measured flux current id, the measured torque current iq, the reference flux current idref and the reference torque current iqref.

(18) The reference torque current and flux current are expressed by the following relationship:

(19) $i_{\mathrm{dq}}^{\mathrm{ref}}=\{\begin{array}{cc}{i}_{\mathrm{dqMax}}\frac{t}{t_i}& \mathrm{if}t<t_i\\ i_{\mathrm{dqMax}}& \mathrm{if}{t}_{i}t{T}_{\mathrm{pw}}+T_{\mathrm{mw}}+T_{\mathrm{DcCurr}}\\ 0& \mathrm{otherwise}\end{array}$
In which: i.sub.dMax is the maximum value of the current on the axis d; i.sub.qMax is the maximum value of the current on the axis q; t.sub.i is the ramp time of the current on starting; T.sub.DcCurr is the time for which the current is maintained at the end of the alignment sequence. The purpose of this DC current at the end of the alignment sequence is to ensure that the motor is stopped at the desired position.

(20) As a variant embodiment, determining the voltage Vdq without control of the current (i.e. in an open loop, without measurement of the currents) consists in: determining (block B5) the voltage in proportion to the reference speed (U/F type control law).

(21) Based on the voltage Vdq and the determined reference position, the control method is able to determine (block B7) the voltages to be applied to the three output phases with the aim of allowing the rotor to be aligned with a known position. The output voltages are expressed in the following manner:

(22) $\left(\begin{array}{c}{v}_a\\ v_b\\ v_c\end{array}\right)=\left(\begin{array}{ccc}1& 0& \frac{\sqrt{2}}{2}\\ -\frac{1}{2}& \frac{\sqrt{3}}{2}& \frac{\sqrt{2}}{2}\\ -\frac{1}{2}& -\frac{\sqrt{3}}{2}& \frac{\sqrt{2}}{2}\end{array}\right)\left(\begin{array}{cc}\cos {}_S& -\sin {}_S\\ \sin {}_S& \cos {}_S\end{array}\right)\left(\begin{array}{c}{v}_d\\ v_q\end{array}\right)$

(23) FIGS. 4A to 4D, 5A to 5D and 6A to 6D illustrate simulation results for various operating cases.

(24) In a first operating case illustrated by FIGS. 4A to 4D, the generated voltage Vdq follows a constant (FIG. 4A) and the reference speed follows a predefined class C0 profile (FIG. 4B). FIG. 4C shows that the actual position of the rotor reaches the reference position at the end of the starting process. FIG. 4D shows that the torque C remains constant and that the starting process used does not generate jolts in the motor.

(25) In a second operating case illustrated by FIGS. 5A to 5D, the generated voltage Vdq follows a constant (FIG. 5A) and the reference speed follows a predefined class C1 profile (FIG. 5B). FIG. 5C shows that the actual position of the rotor reaches the reference position at the end of the starting process. FIG. 5D shows that the torque C remains constant and that the starting process used does not generate jolts in the motor.

(26) In a third operating case illustrated by FIGS. 6A to 6D, the generated voltage Vdq follows a trajectory that is not constant, but continuous (FIG. 6A), and the reference speed follows a predefined class C1 profile (FIG. 6B). FIG. 6C shows that the actual position of the rotor reaches the reference position at the end of the starting process. FIG. 6D shows that the torque C remains constant and that the starting process used does not generate jolts in the motor.

(27) In FIG. 2, it can be noted that the determined reference position s with which the rotor is aligned allows the actual position of the rotor (block B8) to be directly deduced, which may be of use in controlling the motor in normal operation.

(28) The following demonstration makes it possible to show that: there are equilibrium points in the system, depending on the load applied to the motor and voltage applied thereto; these equilibrium points are stable or unstable; the equilibrium point that interests us (minimum angle error) is stable and attainable.

(29) The equations for a synchronous motor in a rotating frame of reference (FIG. 3) are written as follows:

(30) $\{\begin{array}{c}\frac{d}{\mathrm{dt}}{}_{\mathrm{dq}}=u_{\mathrm{dq}}-{\mathrm{Ri}}_{\mathrm{dq}}-{}_s{\mathrm{��}}_{\mathrm{dq}}-{\mathrm{��}}_{}{}_M\\ \frac{J_M}{n_p}\frac{d}{\mathrm{dt}}=\frac{3}{2}{n}_p{i}_{\mathrm{dq}}^T\mathrm{��}\left({}_{\mathrm{dq}}+{}_{}{}_M\right)-T_L-f\\ \frac{d}{\mathrm{dt}}=-{}_s\end{array}$
In which:

(31) $\left(\begin{array}{c}{}_d\\ {}_q\end{array}\right)$
is the electric flux;

(32) $\left(\begin{array}{c}{i}_d\\ i_q\end{array}\right)$
is the current of the motor;

(33) $\left(\begin{array}{c}{}_M\\ 0\end{array}\right)$
is the flux of the permanent magnet;

(34) $\left(\begin{array}{c}{u}_d\\ u_q\end{array}\right)$
is the voltage of the motor in the rotating frame of reference; R, Ld, Lq and .sub.M are the electrical parameters of the motor; J.sub.M and n.sub.p are the mechanical parameters of the motor; f is the coefficient of friction; .sub.L is the load torque;

(35) 0${\mathrm{��}}_{\mathrm{dq}}=\left(\begin{array}{cc}{L}_d& 0\\ 0& L_q\end{array}\right)=\mathrm{��}-=\left(\begin{array}{cc}-& 0\\ 0& +\end{array}\right),=\left(L_q+L_d\right)/2,=\left(L_q-L_d\right)/2;$${}_{\mathrm{dq}}={}_{}{\mathrm{��}}_{\mathrm{dq}}{}_{-}{i}_{\mathrm{dq}}=i_{\mathrm{dq}}-{}_{}{}_{-}{i}_{\mathrm{dq}};$ .sub.s is the angle of the control, i.e. the reference position; is the actual position of the rotor; =.sub.s;

(36) ${}_s=\frac{d{}_s}{\mathrm{dt}},{}_s=\frac{d}{\mathrm{dt}};$$\mathrm{��}=\left(\begin{array}{cc}1& 0\\ 0& 1\end{array}\right),\mathrm{��}=\left(\begin{array}{cc}0& -1\\ 1& 0\end{array}\right),=\left(\begin{array}{cc}1& 0\\ 0& -1\end{array}\right);$${}_{}=\left(\begin{array}{cc}\cos & -\sin \\ \sin & \cos \end{array}\right).$

(37) Control of the motor is carried out via the input voltage and u.sub.dq and the reference speed .sub.s. As the electrical part is the fastest, and without loss of generality, we consider that the current of the motor rapidly converges towards the reference of the current:
i.sub.dq=.sub.dq
In which .sub.dq is the reference of the current.

(38) By way of example, the proof of stability is detailed below for a surface synchronous motor with the following characteristics: L.sub.d=L.sub.q=L and =0.

(39) Thus, to prove the convergence of the angle, it is necessary to study the mechanical equations for the motor, which in this case are written as follows:

(40) $\{\begin{array}{c}\frac{J_M}{n_p}\frac{d}{\mathrm{dt}}=\frac{3}{2}{n}_p{\stackrel{\_}{i}}_{\mathrm{dq}}^T\mathrm{��}\left({\stackrel{\_}{}}_{\mathrm{dq}}+{}_{}{}_M\right)-T_L-f\\ \frac{d}{\mathrm{dt}}=-{}_s\end{array}$
Where .sub.dq=L.sub.dq

(41) Equilibrium Points:

(42) In this case, the equilibrium point is defined by:

(43) $\{\begin{array}{c}0=\frac{3}{2}{n}_p{\stackrel{\_}{i}}_{\mathrm{dq}}^T\mathrm{��}\left(L{\stackrel{\_}{i}}_{\mathrm{dq}}+{}_{{}^{\mathrm{eq}}}{}_M\right)-T_L-f{}^{\mathrm{eq}}\\ 0={}^{\mathrm{eq}}-{}_s\end{array}$
Where .sup.eq and .sup.eq are the equilibrium positions of the system.

(44) We propose to write the references of the currents in polar form as follows:
.sub.d=I cos
.sub.q=I sin

(45) Thus, the equilibrium is defined by:

(46) $\{\begin{array}{c}0=\frac{3}{2}{n}_p{}_{M}I\sin \left(-{}^{\mathrm{eq}}\right)-T_L-f{}_s\\ {}^{\mathrm{eq}}={}_s\end{array}$

(47) Finally we get:

(48) $\{\begin{array}{c}\sin \left(-{}^{\mathrm{eq}}\right)=\frac{T_L+f{}_s}{\frac{3}{2}{n}_p{}_{M}I}\\ {}^{\mathrm{eq}}={}_s\end{array}$

(49) There are two possible equilibrium points:
.sup.eq=.sub.0 or .sup.eq=+.sub.0

(50) Where .sub.0=arcsin

(51) $\left(\frac{{}_L+f{}_s}{\frac{3}{2}{n}_p{}_{M}I}\right),$
it may be noted that

(52) $-\frac{}{2}{}_0\frac{}{2}$

(53) Stability Around the Equilibrium Points:

(54) The system is written as follows:

(55) $\{\begin{array}{c}\frac{J_M}{n_p}\frac{d}{\mathrm{dt}}=\frac{3}{2}{n}_p{}_{M}I\left(\sin \left(-\right)-\sin {}_0\right)-f\left(-{}_s\right)\\ \frac{d}{\mathrm{dt}}=-{}_s\end{array}$

(56) The linearization of this system around the equilibrium (.sup.eq, .sup.eq) gives:

(57) $\{\frac{d}{\mathrm{dt}}\left(\begin{array}{c}\\ \end{array}\right)=\left(\begin{array}{cc}-\frac{{\mathrm{fn}}_p}{J_M}& -\frac{3n_p^2{}_{M}I}{2J_M}\cos \left(-{}^{\mathrm{eq}}\right)\\ 1& 0\end{array}\right)\left(\begin{array}{c}\\ \end{array}\right)$
Where =.sup.eq and =.sup.eq.

(58) The eigenvalues of the stability matrix are given by:

(59) 0$X^2+\frac{{\mathrm{fn}}_p}{J_M}X+\frac{3n_p^2{}_{M}I}{2J_M}\cos \left(-{}^{\mathrm{eq}}\right)=0$

(60) The system is stable if the three coefficients 1,

(61) $\frac{{\mathrm{fn}}_p}{J_M}\mathrm{and}\frac{3n_p^2{}_{M}I}{2J_M}\cos \left(-{}^{\mathrm{eq}}\right)$
are positive.

(62) By definition of the equilibrium positions, the equilibrium .sup.eq=.sub.0 is stable while the equilibrium .sup.eq=+.sub.0 it is unstable.

(63) As a result, the only stable equilibrium position is .sup.eq=.sub.0. The solution is therefore:
=.sub.s+.sub.0.
Thus, by using this expression for the angle, we get the position of the rotor.