INVERTED THREE-STAGE DOHERTY AMPLIFIER

Abstract

An inverted three-stage Doherty amplifier is disclosed. The amplifier provides an input power divider, a carrier amplifier, two peak amplifiers, and an output combiner. The output combiner includes five quarter-wavelength (/4) lines, three of which correspond to three amplifiers, one of rest two /4 lines combines an output of the carrier amplifier with an output of the first peak amplifier, the last /4 line combines the combined output of the carrier amplifier and the first peak amplifier with an output of the second peak amplifier. The five /4 lines have respective impedance to optionally adjust output impedance of the respective amplifiers.

Claims

1. An inverted three-stage Doherty amplifier that outputs an amplified signal by receiving an input signal, comprising: an input power divider that receives the input signal and outputs three divided signal, where one of the three divided signal has a phase delayed by /2 from phases of rest of the three divided signals; a carrier amplifier including an offset transmission line, the carrier amplifier receiving one of the rest of the three divided signals; first and second peak amplifiers each including offset transmission lines, the first peak amplifier receiving another of the rest of the three divided signals, the second peak amplifier receiving the one of the three divided signals, the offset transmission line in the carrier amplifier and the offset transmission lines in the first and second peaking amplifiers converting output impedance thereof to be short-circuits when the carrier amplifier and the first and second peaking amplifiers are turned off; and an output combiner that combines outputs of the carrier amplifier and the first and second peak amplifiers, the output combiner including, a first quarter-wavelength line connected with the carrier amplifier, a second quarter-wavelength line connected with the first peak amplifier, a third quarter-wavelength line connected with the second peak amplifier, a fourth quarter-wavelength line connected with the first quarter-wavelength line and the second quarter-wavelength line, the fourth quarter-wavelength line combining an output of the carrier amplifier provided through the first quarter-wavelength line with an output of the first peak amplifier provided through the second quarter-wavelength line, and a fifth quarter-wavelength line connected with the third quarter-wavelength line and the fourth quarter-wavelength line, the fifth quarter-wavelength line combining an output of the second peak amplifier provided through the third quarter-wavelength line with a combined output of the carrier amplifier and the first peak amplifier provided though the fourth quarter-wavelength line; and outputting a combined output of the carrier amplifier and the first and second peak amplifiers, wherein the first peak amplifier has a size greater than a size of the carrier amplifier; and wherein the second peak amplifier has a size greater than the size of the first peak amplifier.

2. The inverted three-stage Doherty amplifier according to claim 1, wherein the carrier amplifier and the first and second peaking amplifiers in sizes thereof have a ratio of 1:m1:m2, and wherein the fourth quarter-wavelength line and the fifth quarter-wavelength line have impedance of (1+m.sub.2/m.sub.1)*Z.sub.0 and (1+m.sub.1/m.sub.2)*Z.sub.0, respectively, where Z.sub.0 is impedance of a load for the inverted three-stage Doherty amplifier.

3. The inverted three-stage Doherty amplifier according to claim 2, wherein the fifth quarter-wavelength line and the fourth quarter-wavelength line have impedance in a ration of 2.

4. The inverted three-stage Doherty amplifier according to claim 2, wherein the carrier amplifier and the first and second peak amplifiers in the respective sizes thereof satisfy a condition of (1+m.sub.1)=m.sub.2.

5. The inverted three-stage Doherty amplifier according to claim 1, wherein the input power divider includes a 90 hybrid coupler including a transmitter port and a coupled port, the carrier amplifier and the first peak amplifier receiving one of the divided signal output from the transmitted port, the second peak amplifier receiving another of the divided signal output from the coupled port.

Description

BRIEF DESCRIPTION OF DRAWINGS

[0006] FIG. 1 shows a functional block diagram of a conventional three-stage inverted Doherty amplifier;

[0007] FIG. 2 compares behaviors of efficiencies of the Doherty amplifier of the embodiments with that of the conventional Doherty amplifier;

[0008] FIG. 3 shows a functional block diagram of a three-stage inverted Doherty amplifier according to an embodiment of the present invention;

[0009] FIG. 4 shows a functional block diagram of a three-stage inverted Doherty amplifier according to another embodiment of the present invention; and

[0010] FIG. 5A schematically shows a circuit diagram of an offset unit for a carrier amplifier and also a peak amplifier, and FIG. 5B shows an impedance behavior of the offset unit shown in FIG. 5A.

DESCRIPTION OF EMBODIMENTS

[0011] Next, some embodiments according to the present invention will be described as referring to accompanying drawings. In the description of the drawings, numerals or symbols same with or similar to each other will refer to elements same with or similar to each other without duplicating explanations.

[0012] FIG. 1 shows a functional block diagram of a three-stage modified inverted Doherty amplifier 1000 with a conventionally known configuration, where the quarter wavelength (/4) lines are added in the outputs of the carrier amplifier 10.sub.0 and the peak amplifiers, 10.sub.1 and 10.sub.2, to provide a proper load modulation ratio. In inverted Doherty architectures, in view of the presence of parasitic capacitance due to a shunt drain-source, inductance attributed to a series bonding wire and a package lead, a design to set the output of the amplifiers to be a short circuit becomes easier compared with a design to set the output impedance to be an open circuit when the amplifiers are turned off in a low power region. In this case, the shunt capacitor and series inductor compose the series resonant circuit with the series resonance frequency close to the carrier frequency. By using an additional series offset line in an offset unit 30; the resonant point may be properly tuned to the carrier frequency.

[0013] Explaining further specifically, FIG. 5A schematically illustrates a primary portion of a circuit diagram around an FET implemented within the amplifiers, 10.sub.0 to 10.sub.3, while, FIG. 5B indicates a smith chart of the circuit shown in FIG. 5A. The FET in the amplifier inevitably accompanies with the junction capacitance between the drain and the source, and the inductance due to the bonding wire to extract an output from the drain. Assuming the output impedance of the FET seeing the inside at the drain thereof to be Z.sub.OUT.sub._.sub.OFF, this impedance Z.sub.OUT.sub._.sub.OFF shifts from the open circuit on the smith chart as shown in FIG. 5B.

[0014] Referring to FIG. 5A, the FET in the drain thereof couples with a matching circuit including, for instance, a capacitor C and an inductor L, where the capacitor C is not the junction capacitance between the drain and the source of the FET but the inductor L corresponding to the inductance attributed to the bonding wire connected between the drain of the FET and the offset transmission line TLR.sub.n. The matching circuit moves, or rotates clockwise from the Z.sub.OUT.sub._.sub.OFF to the Z.sub.LC.sub._.sub.OFF, that is, the impedance Z.sub.LC.sub._.sub.OFF corresponds to impedance seeing the FET at the end of the offset transmission line TLR.sub.n.

[0015] The offset transmission lines, TLR.sub.0 to TLR.sub.2, in the offset unit 30 have the electrical length corresponding to rotate the point Z.sub.LC.sub._.sub.OFF to the short circuit (Z=0). Because the point Z.sub.LC.sub._.sub.OFF positions in the edge on the smith chart, the offset transmission lines, TLR.sub.0 to TLR.sub.2, have the characteristic impedance of Z.sub.0, and the electrical length L.sub.OFF so as to rotate the point from the point Z.sub.LC.sub._.sub.OFF to the short circuit (Z=0) in the left end, where an example shown in FIG. 5B has the electrical length about /16.

[0016] Referring back to FIG. 1, in the description below, CA means a carrier amplifier; while, PA means a peak amplifier. All amplifiers, the CA and the PAs, are turned on at saturation, the CA is turned on only to provide a maximum efficiency at a maximum back-off point, and both CA and the PA.sub.1 are turned on, with PA.sub.2 being turned off, to provide intermediate efficiency. The half-wavelength line 20a in the input path of the CA 10.sub.0 is used to compensate for the delay provided by the output combiner 40.

[0017] In the circuit arrangement shown in FIG. 1, setting a ratio of device sizes to be 1:1.7:1.7 for the respective amplifiers, 10.sub.0 to 10.sub.2; the first peak efficiency is obtained at a back-off point of 4.2 dB where the CA 10.sub.0 and the first PA 10.sub.1 are turned on, and the maximum efficiency at the back-off point is provided to be 8.5 dB where only the CA 10.sub.0 is turned on, as shown in FIG. 2. However, the output combiner 40 includes six quarter-wavelength lines, TL.sub.1, TL.sub.2, TL.sub.A, TL.sub.B, TL.sub.C, and TL.sub.T, which makes the final implementation inconvenient in terms of a size and a cost of a Doherty amplifier. Besides, the back-off point that provides the maximum efficiency is not fallen down enough to provide high efficiency for modem LTE signals that request considerably high peak-to-average power ratio (PAR) of, for instance 9 dB or higher.

[0018] FIG. 3 shows a functional block diagram of an inverted Doherty amplifier 100 according to an embodiment of the present invention that includes a CA 10.sub.0, two PAs, 10.sub.1 and 10.sub.2, an input power divider 20, an offset unit 30, and an output combiner 40. The CA 10.sub.0 and the two PAs, 10.sub.1 and 10.sub.2, each implementing an input matching circuit and an output matching circuit therein, are configured to operate such that the PAs, 10.sub.1 and 10.sub.2, switch on sequentially in this order as increasing the input power. The input power divider 10 is coupled between an input terminal RF.sub.IN and respective inputs of the CA 10.sub.0 and the two PAs, 10.sub.1 and 10.sub.2; the outputs of the CA 10.sub.0 and the two PAs, 10.sub.1 and 10.sub.2, are coupled through an output combiner 40 to an output terminal RF.sub.OUT. The second PA 10.sub.2 is coupled with the input power divider 20 through a transmission line TL.sub.IN with a quarter-wavelength for a signal subject to the Doherty amplifier 100.

[0019] The CA 10.sub.0 and the first PA 10.sub.1 are coupled with the first common node N.sub.1 through respective offset lines, TLR.sub.0 and TLR.sub.1, and impedance converters, TL.sub.0 and TL.sub.P1, which also includes an additional impedance converter T.sub.C connected in series to the first common node N.sub.1, where those paths and elements including the CA 10.sub.0 and the first PA 10.sub.1 constitute the first path of the present invention. The second path includes the second PA 10.sub.2, an offset line TLR.sub.2 and another impedance converter TL.sub.P2. Both the first path and the second path are combined at the second common node N.sub.2. That is, the other impedance converter TL.sub.P2 in the second path is connected with the second common node N.sub.2, and becomes an open circuit when the second PA 10.sub.2 is turned off because impedance viewing the second PA 10.sub.2 at an end of the offset line TLR.sub.2 becomes a short circuit. Impedance of the transmission lines in the output combiner 40 are chosen so as to provide power combination when the CA 10.sub.0 and the two PAs, 10.sub.1 and 10.sub.2, are turned on. The quarter-wavelength line TL.sub.T connected between the second common node N.sub.2 and the output terminal RF.sub.OUT provides the output impedance transformation.

[0020] The inverted three-stage Doherty amplifier shown in FIG. 3 has an extended back-off with sufficient efficiency. Here, the arrangement includes only one quarter-wavelength line TL.sub.IN between the input power divider 20 and the input of the second PA 10.sub.2 in addition to five (5) quarter-wavelength lines in the output combiner 40, which may optionally set the back-off point providing the maximum efficiency by adequately selecting the device size of the CA 10.sub.0 and characteristic impedance Z.sub.C of the quarter-wavelength line TL.sub.0.

[0021] Specifically, when the devices in the CA 10.sub.0 and the PAs, 10.sub.1 and 10.sub.2, in sizes thereof have a ratio of 1:m.sub.1:m.sub.2, the impedance, Z.sub.C and Z.sub.P1, of the transmission lines, TL.sub.0 and TL.sub.1, are preferably set to be:

Z.sub.C=Z.sub.0*(1+m.sub.2/m.sub.1), and

Z.sub.P1=Z.sub.0*(1+m.sub.1/m.sub.2),

where Z.sub.0 is load impedance of the Doherty amplifier 100.

[0022] When both PAs, 10.sub.1 and 10.sub.2, are turned off, the CA 10.sub.0 sees the load impedance of 1+m.sub.2/m.sub.1).sup.2/2 to provide a back-off point where the efficiency becomes a maximum because a ratio in impedance of the transmission lines, TL.sub.T and T.sub.C, is set to be Z.sub.T/Z.sub.C=2. For example, assuming a ratio of the device sizes to be 1:3:4, the back-off point, at which a maximum efficiency is given, becomes 12 dB. In another example, when the devices have a ratio of 1:7:8 in sizes thereof, the back-off point may expand to 18 dB, as shown in FIG. 2.

[0023] When the CA 10.sub.0 and the first PA 10.sub.1 are turned on but the second PA 10.sub.2 is turned off, the former two amplifiers, 10.sub.0 and 10.sub.1, behave as an un-balanced Doherty amplifier. Besides, when the ratio in the device sizes in the two amplifiers, 10.sub.0 and 10.sub.1 is set to be 1:3, the back-off range becomes 6 dB, while, the ratio of 1:7 brings the back-off range of 12 dB. When the CA 10.sub.0 and the two PAs, 10.sub.1 and 10.sub.2, are all turned on, a composite amplifier of the CA 10.sub.0 with the first PA 10.sub.1, and the second PA 10.sub.2 may behave as a balanced Doherty amplifier to show an additional back-off range of 6 dB because a sum of the device sizes for the CA 10.sub.0 and the first PA 10.sub.1 becomes equal to the size the second PA 10.sub.2 in the examples above described. Accordingly, the former example where the ratio of the device sizes is 1:3:4 shows the back-off range of 6 dB 6 dB=12 dB, while, the latter example of the ratio of 1:7:8 gives the back-off range of 12 dB 6 dB=18 dB.

[0024] All amplifiers include the input matching circuits, whose configurations fully depend on the corresponding device impedance for particular applications to match the source with the impedance of 50 . The offset lines, TLR.sub.0 to TLR.sub.2, are necessary to provide low impedance at the outputs thereof when the PAs, 10.sub.1 and 10.sub.2 are turned off. All amplifiers, 10.sub.0 to 10.sub.2, are turned on at the saturation, the CA 10.sub.0 is turned on only to provide efficiency peak at maximum back-off when the first and second PAs, 10.sub.1 and 10.sub.2, are turned off, and both CA 10.sub.0 and the first PA 10.sub.1 are turned on to operate as an un-balanced Doherty amplifier and provide an efficiency peak at inter mediate efficiency peak. In this case, the output matching circuit of CA 10.sub.0 in conjunction with the corresponding quarter-wavelength line TL.sub.0 connected in series thereto in the output combiner 40 should provide the impedance information when the high impedance is seen by the current source of the transistor CA.

[0025] FIG. 4 shows another embodiment of the modified inverted three-stage Doherty configuration with extended high-efficiency back-off point where the CA 10.sub.0 and the first PA 10.sub.1 are connected together to one output port of the 90 hybrid coupler 20a, while the second PA 10.sub.2 is connected to another output port of the input coupler 20a. In this case, an additional quarter wave transmission line TL.sub.IN at the input diving circuit becomes unnecessary.

[0026] While particular embodiments of the present invention have been described herein for purposes of illustration, many modifications and changes will become apparent to those skilled in the art. Accordingly, the appended claims are intended to encompass all such modifications and changes as fall within the true spirit and scope of this invention.