RESONANT CONVERTER HAVING A TRANSFORMER WITH CENTRAL POINT TAP

Abstract

In order to set the output voltage of a resonant converter to a desired value by means of a simple additional circuit while the resonant converter is in open circuit operation, it is intended that at least one capacitor each (C1, C2) is connected in parallel to the electrical switching elements (S1, S2) of the secondary side of the resonant converter (1).

Claims

1. Resonant converter with a transformer (T) with center tap and a resonant circuit, wherein the center point (M) of the secondary side of the transformer (T) is connected via a first output line (10) to a first output terminal (12), and the two outer connections (A1, A2) of the secondary side of the transformer (T) are connected each via an electrical switching element (S1, S2) and are connected via a second output line (11) to a second output terminal (13), wherein between the first output to (12) and the second output terminal (13) there is an output voltage (UA) so that the first output terminal (12) is guided to the outside directly via the first output line (10) without any additional circuit between the first output terminal (12) and the second output terminal (13) in the form of a smoothing capacitor on the output side, and wherein at least one capacitor (C1, C2) is connected in parallel to the electrical switching elements (S1, S2) in order to maintain the output voltage (UA) when the resonant converter is in open circuit operation.

2. Resonant converter according to claim 1, wherein parallel to the electrical switching elements (S1, S2) there is at least one discharge resistor connected (R5, R6).

3. Resonant converter according to claim 1, wherein at least two series-connected resistors (R3, R4) are connected between the two outer connections (A1, A2) of the secondary side of the transformer (T) for forming a measurement point (P) between the two resistors (R3, R4, and a voltage measuring unit (V) is provided, measuring the voltage (UP) between the measuring point (P) and the second output terminal (13) that corresponds to the output voltage (UA) between the first output terminal (12) and the second output terminal (13).

4. Resonant converter according to claim 3, wherein at least one further resistor (R2) is connected between the measurement point (P) and the second output terminal (13).

5. A method for operating a resonant converter, wherein an output voltage (UA) is created between a first output terminal (12) connected to a center point (M) and a second output terminal (13) connected to the two outer connections (A1, A2) of the secondary side of the transformer (T) via an electrical switching element (S1, S2) each, wherein the output voltage (UA) is maintained when the resonant converter is in open circuit operation by using capacitors (C1, C2) connected in parallel to the electrical switching elements (S1, S2).

Description

[0012] The present invention will be described in further detail below referring to FIGS. 1 to 7, which demonstrate advantageous embodiments of the invention that are exemplary and schematic in nature and not intended to limit the scope of the invention. Shown are:

[0013] FIG. 1, showing a typical resonant converter according to the prior art;

[0014] FIG. 2, showing a voltage measurement that is customary in the prior art taken at the secondary side of a transformer with center tap;

[0015] FIG. 3, showing the additional wiring customary in the prior art for controlling the output voltage of a series-parallel resonant converter in the no-load state;

[0016] FIG. 4, showing a circuit arrangement with a transformer with center tap and voltage measurement of the output voltage according to the invention;

[0017] FIG. 5, showing a series-parallel resonant converter with secondary wiring for adjusting the no-load voltage;

[0018] FIG. 6, showing the voltage curves resulting in the series-parallel resonant converter in the no-load state; and

[0019] FIG. 7, showing a series-parallel resonant converter having the measurement apparatus according to the invention for measuring voltage and the secondary wiring for controlling the output voltage in the no-load state.

[0020] FIG. 4 shows a circuit arrangement 8 having a transformer T with center tap on the secondary side. The secondary side of the transformer T with center tap has at least three connections: one for the center point M and two at the ends of the windings on the secondary side, wherein these connections are designated as outer connection.

[0021] But it is noted in general that a transformer with center tap within the meaning of the invention also includes the use of two or more transformer windings with a joint core, which have the windings on the secondary and primary sides each connected in series (see FIG. 5). Independent transformers with primary windings connected in parallel and secondary windings connected in series are also included. An electrical connection between two windings connected in series on the secondary side then corresponds to the center point M where the first output line 10 can be connected.

[0022] The center point M on the secondary side is routed to the outside via the first output line 10, here a positive output line, as a first output terminal 12, here the positive terminal. The first output line 10 therein is not routed via a substrate 3, as, for example, a circuit board, but directly as a line to the outside. In this context, a smoothing capacitor between the first output terminal 12 and the second output terminal 13 is omitted on the output side. The two outer, not series-connected, connections A1, A2 of the secondary side of the transformer 1 are each routed in a manner known in the art to a first connection of a circuit element S1, S2. The respectively second connections of the circuit elements S1, S2 are connected to each other and form the second output terminal 13, here the negative terminal, of the rectifier that is routed to the outside with a second output line 11, here a negative output line.

[0023] If passive circuit elements in the form of diodes are used as electrical circuit elements S1, S2, a known center point rectifier is obtained. If active circuit elements in the form of, for example, semiconductor switches, such as, e.g., MOSFETs, are used as electrical circuit elements S1, S2, a known synchronous rectifier is obtained. As the features of center point rectifiers and synchronous rectifiers are well known in the art and immaterial for purposes of the present invention, they will not be addressed in further detail.

[0024] The circuit elements S1, S2 are disposed on the substrate 3 as is customary in the art. Naturally, the substrate 3 can be configured as divided. Particularly in the case of active circuit elements S1, S2, the power part with the active circuit elements S1, S2 is often disposed on a separate substrate 3. In addition, an electric measurement apparatus 14 is additionally disposed on the substrate 3 for measuring the output voltage U.sub.A. However, the circuit elements of the secondary side can also be connected to each other by means of copper stirrups. A combination circuit arrangement on the secondary side with a substrate 3 and copper stirrups is also conceivable. For example, the measurement apparatus 14 for measuring the output voltage U.sub.A could be disposed on a substrate 3, and the remainder of the circuit elements could be connected by means of copper stirrups.

[0025] Said measurement apparatus 14 for measuring the output voltage U1, substantially has two resistors R3, R4 that are series-connected between the two outer connections A1, A2 of the secondary side of the transformer T. This way, a measurement point P is created between the two resistors R3, R4, which features a voltage U.sub.P opposite the second output terminal 13 that corresponds to the output voltage U.sub.A applied to the center point M. Said measurement U.sub.P as the measurement point P can be measured by any voltage measurement unit V and provided as an analog or digital measured value MW. For example, the voltage measurement unit V can be configured as an amplifier circuit with an operational amplifier, wherein the output of the amplifier circuit is digitized in an analog-digital transformer and routed to the outside as the digital measured value MW.

[0026] If the two resistors R3, R4 are equal, the voltage U.sub.P at the measurement point P corresponds to the output voltage U.sub.A at the center point M, meaning, in the shown embodiment of the voltage, at the first output terminal 12. If the resistors R3, R4 are not equal, a voltage that corresponds to the ratio of the resistors R3, R4 becomes manifest at the measurement point P. In both cases, it is thus possible to measure the output voltage U.sub.A at the measurement point P by measuring the voltage U.sub.P of the measurement point P opposite the second output terminal 13, as hinted at in FIG. 4.

[0027] The voltage U.sub.P at measurement point P can be measured directly; but a measurement by means of a voltage divider is also conceivable. This allows for the use of a voltage measurement unit V with a reduced input range, thereby achieving technical circuit simplifications. To this end, it is possible to create a voltage divider between the measurement point P and the second output terminal 13 by means of an additional resistor R2, as hinted at in FIG. 4. The resistor R2 therein, in conjunction with the resistors R3 and R4, achieves a corresponding reduction of the voltage U.sub.P at the measurement point P that, however, is still proportionate relative to the output voltage U.sub.A. If the voltage measurement unit V requires a still lesser input voltage, it is possible to distribute the resistor R2 at an appropriate ratio over two resistors to achieve an adjustment to the input voltage range of the voltage measurement unit V.

[0028] This means, when using a measurement apparatus 14 for the measurement of the voltage of the output voltage U.sub.A, it follows, correspondingly, that routing the first output line 10 via the substrate 3 or connecting the first output line 10, as seen in the prior art, to the substrate 3 or the voltage measurement unit V via an additional connecting line 5 is no longer necessary.

[0029] FIG. 5 shows a series-parallel resonant converter 1 with a series oscillator circuit on the primary side consisting of a choke L.sub.R, vibrating capacitor C.sub.R and the primary side of the transformer T, a parallel oscillator circuit on the secondary side consisting of vibrating capacitor C.sub.P and the secondary side of the transformer T, and a center point rectifier (meaning with diodes D1, D2 as electrical circuit elements S1, S2) on the secondary side. The primary side is not completely displayed in the present figure; particularly, the electrical circuit for generating the shown input voltage U.sub.E, which is known in the art, has been omitted. It is understood that the oscillator circuit on the primary side can also be configured as a parallel oscillator circuit, which is known in the art, where the vibrating capacitor C.sub.R is, for example, connected in parallel relative to the primary side of the transformer T. Similarly, the oscillator circuit can be configured differently or not at all on the secondary side, which is also known in the art. Similarly, the oscillator circuit on the secondary side could be configured differently or not at all, which also known in the art. Likewise, the polarity of the diodes D1, D2 can be reversed, or the same could be replaced with other electrical circuit elements S1, S2.

[0030] To maintain the output voltage U.sub.A at a desired value in a no-load state, a secondary wiring 15 is intended according to the invention wherein at least one capacitor C1, C2 is connected parallel relative to the electrical circuit elements S1, S2, here diodes D1, D2. Therefore no separate connection is necessary between the first output line 10 and substrate 3 for the secondary wiring 15 for adjusting the no-load voltage.

[0031] A desired output voltage U.sub.A is to be maintained in the no-load state on the resonant converter 1. To this end, voltage pulses are applied for a specified time span t.sub.1 on the primary side of the transformer T that excite the resonant circuit on the primary side. The excitation results in an oscillation on the secondary side of the transformer T. In the no-load state, the voltages that are applied to the capacitors C1, C2 also vibrate around the level of the output voltage U.sub.A. The capacitors C1, C2 are thereby charged during the excitation on the primary side for the time span t.sub.1 which also results in an increase of the no-load voltage at the output U.sub.A. The excitation on the primary side is then interrupted for a second time span t.sub.2. During this phase, the capacitors C1, C2 are discharged. To this end, it is possible to provide the discharge resistors R5, R6, as hinted at in FIG. 5. Without the discharge resistors R5, R6, the capacitors C1, C2 are discharged according to their self-discharge characteristics. If the secondary wiring 15 is implemented together with the measurement apparatus 14 for measuring the output voltage U.sub.A (see FIG. 7), the resistors R2, R3, R4 of the measurement apparatus 14 serve simultaneously as bleeder resistors. During the discharge action of the capacitors C1, C2, the no-load voltage U.sub.A decreases at the output. A medium output voltage U.sub.A at the output during open circuit operation is the result. This means by adjusting the voltage pulses U.sub.E, pulse frequency and time spans t.sub.1, t.sub.2, it is possible to maintain the output voltage U.sub.A at a desired value. During normal operation (with a connected load at the output), this secondary wiring 15 is without influence. The voltage curves in the no-load state that result, for example, at a series-parallel resonant converter are depicted schematically in FIG. 6.

[0032] The two capacitors C1, C2 of the secondary wiring 15 therein can feature smaller dimensions than what has been the case with the smoothing capacitor C3 in the usual circuit according to the prior art (see FIG. 3). This also allows for saving space on the substrate 3 by omitting the smoothing capacitor C3. Aside from this, it is now also possible to reduce the thermal load of the substrate 3, which also results in a possible size reduction of the substrate.

[0033] The smaller capacitance values C1, C2 compared to the smoothing capacitor C3, however, also cause in addition that the output voltage U.sub.A to decreases more quickly in the no-load state, which is especially advantageous for applications in welding current sources, because it is thereby possible to reach the permitted maximum voltage after the end of the welding action more quickly.

[0034] Of course, the measurement apparatus 14 for measuring voltage and the secondary wiring 15 for controlling the output voltage U.sub.A in the no-load state can also be combined, as shown in FIG. 7, using a resonant converter 1 with center point rectifier. A combination of this kind is particularly advantageous because, this way, it is possible to regulate the output voltage U.sub.A also in the no-load state (no-load voltage) to have a desired value by measuring the voltage U.sub.P at the measurement point P that corresponds to the output voltage U.sub.A, and/or it is possible to ensure a desired value of the no-load voltage.