Method of controlling single-phase voltage source AC/DC converter and interconnection system

Abstract

A method of controlling a single-phase voltage source AC/DC converting circuit has internal equivalent impedance as seen from an AC terminal, for converting power from a DC voltage source connected to a DC terminal to single-phase AC power or for converting single-phase AC power from a single-phase AC source connected to the AC terminal to DC power in accordance with a pulse width of a gate signal generated based on a PWM command.

Claims

1. A method of controlling a single-phase voltage source AC/DC converting circuit, which has internal equivalent impedance as seen from an AC terminal, for converting power from a DC voltage source connected to a DC terminal to single-phase AC power or for converting single-phase AC power from a single-phase AC source connected to the AC terminal to DC power in accordance with a pulse width of a gate signal generated based on a PWM command, the method comprising steps of: outputting a first axis voltage command to control amplitude of a single-phase AC output voltage at the AC terminal and a second axis voltage command to control a single-phase AC frequency at the AC terminal; outputting a voltage command signal generated so that the amplitude of the single-phase AC output voltage at the AC terminal approaches the first axis voltage command and a frequency command signal generated so that the single-phase AC frequency at the AC terminal approaches the second axis voltage command based on the first axis voltage command and the second axis voltage command, which are input, the single-phase AC output voltage at the AC terminal, and a phase difference voltage corresponding to phase difference between the single-phase AC output voltage at the AC terminal and an internal electromotive voltage of the single-phase voltage source AC/DC converting circuit; determining an electrical angle of the internal electromotive voltage of the single-phase voltage source AC/DC converting circuit based on a reference frequency of a single-phase AC output frequency at the AC terminal, the frequency command signal, and the phase difference voltage and generating a generated electrical angle; and outputting a signal generated so that the amplitude, a frequency, and a phase of the single-phase AC output voltage at the AC terminal approach a synthesized value of a reference voltage of the single-phase AC output voltage at the AC terminal, the voltage command signal, and the generated electrical angle as the PWM command based on the single-phase AC output voltage at the AC terminal, the generated electrical angle, and the voltage command signal, wherein, when converting power from the DC voltage source connected to the DC terminal to single-phase AC power, the second axis voltage command is a value obtained by integrating a difference between a DC voltage command value to specify a voltage at the DC terminal and a DC voltage detection value that is the voltage at the DC terminal, wherein, when the DC voltage detection value increases and an error between the DC voltage detection value and the DC voltage command value is negative, the second axis voltage command is increased so that active power is increased, and wherein, when the DC voltage detection value decreases and the error between the DC voltage detection value and the DC voltage command value is positive, the second axis voltage command is decreased so that active power is decreased, so that the voltage at the DC terminal is maintained at the DC voltage command value.

2. The method of claim 1, wherein the second axis voltage command is expressed by Equation 2:
V^2*(s)=1/Tdc s(V^D*(s)V^D(s))[Equation 2] where, V2* represents the second axis voltage command; VD* represents the DC voltage command value; VD represents the DC voltage detection value; s represents a variable of Laplace transform; Tdc represents an integral time constant; and ^ represents a Laplace transform.

3. A method of controlling a single-phase voltage source AC/DC converting circuit, which has internal equivalent impedance as seen from an AC terminal, for converting power from a DC voltage source connected to a DC terminal to single-phase AC power or for converting single-phase AC power from a single-phase AC source connected to the AC terminal to DC power in accordance with a pulse width of a gate signal generated based on a PWM command, the method comprising steps of: outputting a first axis voltage command to control amplitude of a single-phase AC output voltage at the AC terminal and a second axis voltage command to control a single-phase AC frequency at the AC terminal; outputting a voltage command signal generated so that the amplitude of the single-phase AC output voltage at the AC terminal approaches the first axis voltage command and a frequency command signal generated so that the single-phase AC frequency at the AC terminal approaches the second axis voltage command based on the first axis voltage command and the second axis voltage command, which are input, the single-phase AC output voltage at the AC terminal, and a phase difference voltage corresponding to phase difference between the single-phase AC output voltage at the AC terminal and an internal electromotive voltage of the single-phase voltage source AC/DC converting circuit; determining an electrical angle of the internal electromotive voltage of the single-phase voltage source AC/DC converting circuit based on a reference frequency of a single-phase AC output frequency at the AC terminal, the frequency command signal, and the phase difference voltage and generating a generated electrical angle; and outputting a signal generated so that the amplitude, a frequency, and a phase of the single-phase AC output voltage at the AC terminal approach a synthesized value of a reference voltage of the single-phase AC output voltage at the AC terminal, the voltage command signal, and the generated electrical angle as the PWM command based on the single-phase AC output voltage at the AC terminal, the generated electrical angle, and the voltage command signal, wherein, when converting power from the DC voltage source connected to the DC terminal to single-phase AC power, the second axis voltage command is a value obtained by adding a value obtained by removing a high frequency component of a difference between a DC voltage command value to specify a voltage at the DC terminal and a DC voltage detection value that is the voltage at the DC terminal and a value obtained by integrating the difference, wherein, when the DC voltage detection value increases and an error between the DC voltage detection value and the DC voltage command value is negative, the second axis voltage command is increased so that active power is increased, and wherein, when the DC voltage detection value decreases and the error between the DC voltage detection value and the DC voltage command value is positive, the second axis voltage command is decreased so that active power is decreased, so that the voltage at the DC terminal is maintained at the DC voltage command value.

4. The method of claim 3, wherein the second axis voltage command is expressed by Equation 3:
V^2*(s)=((Kdc/1+TKdcs)(1/Tdcs))(V^D*(s)V^D(s))[Equation 3] where, V2* represents the second axis voltage command; VD* represents the DC voltage command value; VD represents the DC voltage detection value; s represents a variable of Laplace transform; Kdc represents a proportional gain; TKdc represents a first-order lag time constant; Tdc represents an integral time constant; and ^ represents a Laplace transform.

Description

BRIEF DESCRIPTION OF THE DRAWINGS

(1) FIG. 1 is a view illustrating a traditional inverter.

(2) FIG. 2 is a view illustrating details of an automatic voltage regulator (dc-AVR).

(3) FIG. 3 is a view illustrating concurrent control of a DC voltage and reactive power at a single-phase voltage source AC/DC converter, which adopts a method of controlling a single-phase voltage source AC/DC converting circuit according to the present disclosure.

(4) FIG. 4 is a schematic configuration diagram of a single-phase voltage source AC/DC converter, which adopts a method of controlling a single-phase voltage source AC/DC converting circuit according to the present disclosure.

(5) FIG. 5 is a schematic configuration diagram of a single-phase voltage source AC/DC converter, which adopts a method of controlling a single-phase voltage source AC/DC converting circuit according to the present disclosure.

(6) FIG. 6 is a schematic configuration diagram of a single-phase voltage source AC/DC converter, which adopts a method of controlling a single-phase voltage source AC/DC converting circuit according to the present disclosure.

(7) FIG. 7 is a schematic configuration diagram of a single-phase voltage source AC/DC converting circuit to be controlled by the present disclosure.

(8) FIG. 8 is a schematic configuration diagram of a single-phase voltage source AC/DC converting circuit to be controlled by the present disclosure.

(9) FIG. 9 is a schematic configuration diagram of an AC power measuring instrument included in a single-phase voltage source AC/DC converter, which adopts a method of controlling a single-phase voltage source AC/DC converting circuit according to the present disclosure.

(10) FIG. 10 is a schematic configuration diagram of an AC power measuring instrument included in a single-phase voltage source AC/DC converter, which adopts a method of controlling a single-phase voltage source AC/DC converting circuit according to the present disclosure.

(11) FIG. 11 is a view illustrating connection relation of a control block in a method of controlling a single-phase voltage source AC/DC converting circuit according to the present disclosure.

(12) FIG. 12 is a schematic configuration diagram of a phase difference generating circuit included in a single-phase voltage source AC/DC converter, which adopts a method of controlling a single-phase voltage source AC/DC converting circuit according to the present disclosure.

(13) FIG. 13 is a view illustrating a command value arithmetic circuit included in a single-phase voltage source AC/DC converter, which adopts a method of controlling a single-phase voltage source AC/DC converting circuit according to the present disclosure.

(14) FIG. 14 is a view illustrating a command value arithmetic circuit included in a single-phase voltage source AC/DC converter, which adopts a method of controlling a single-phase voltage source AC/DC converting circuit according to the present disclosure.

(15) FIG. 15 is a view illustrating a command value arithmetic circuit included in a single-phase voltage source AC/DC converter, which adopts a method of controlling a single-phase voltage source AC/DC converting circuit according to the present disclosure.

(16) FIG. 16 is a view illustrating a command value arithmetic circuit included in a single-phase voltage source AC/DC converter, which adopts a method of controlling a single-phase voltage source AC/DC converting circuit according to the present disclosure.

(17) FIG. 17 is a view illustrating a command value arithmetic circuit included in a single-phase voltage source AC/DC converter, which adopts a method of controlling a single-phase voltage source AC/DC converting circuit according to the present disclosure.

(18) FIG. 18 is a view illustrating a command value arithmetic circuit included in a single-phase voltage source AC/DC converter, which adopts a method of controlling a single-phase voltage source AC/DC converting circuit according to the present disclosure.

(19) FIG. 19 is a view illustrating a configuration of an interconnection system, which adopts a method of controlling a single-phase voltage source AC/DC converting circuit according to the present disclosure.

(20) FIG. 20 is a simulation result with a single-phase voltage source AC/DC converter, which adopts a method of controlling a single-phase voltage source AC/DC converting circuit according to the present disclosure.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT

(21) Embodiments of the present disclosure are described with reference to the attached drawings. The embodiments hereinafter described are examples of the present disclosure, and the present disclosure is not limited to the following embodiments. Meanwhile, components to which an identical reference numeral is assigned in this description and the drawings are identical to each other. Although the present disclosure is a method of controlling a single-phase voltage source AC/DC converting circuit, the disclosure is described with reference to a single-phase voltage source AC/DC converter including the single-phase voltage source AC/DC converting circuit.

(22) [Single-Phase Voltage Source AC/DC Converter]

(23) FIG. 11 is a view exemplifying connection relation of a control block in a single-phase voltage source AC/DC converter and includes a superior command vector B1, a superior control block B2, an ac-AVR block B3, an ETM-PWM block B4, and a main switch B5. Regarding the ac-AVR block B3, a transformer connected to an output circuit of an inverter is prevented from an hysteretic magnetization by adopting a single-phase ac-AVR having internal equivalent impedance described in Japanese Patent Application Laid-Open No. 2009-201224 as a main part of inductance. In addition, since the internal equivalent impedance can be actualized as a parallel circuit of a resistance component and an inductance component, degree of freedom of design is increased.

(24) A schematic configuration of a single-phase voltage source AC/DC converter according to the present embodiment is illustrated in FIGS. 4 and 5. Then, details of the respective blocks illustrated in FIG. 11 are described.

(25) A single-phase voltage source AC/DC converter 11 illustrated in FIG. 4 includes a single-phase voltage source DC/AC converting circuit 40 having internal equivalent impedance as seen from an AC terminal 22 for receiving power at a DC terminal 21 from a DC voltage source (not illustrated) and converting to single-phase AC power in accordance with a pulse width of a gate signal generated based on a PWM command to output from the AC terminal 22; a phase difference generating circuit 30 having a phase delay single-phase AC generator to generate a delay single-phase alternating voltage of which phase is delayed against a single-phase AC output voltage at the AC terminal 22 for generating a phase difference voltage corresponding to phase difference between the single-phase AC output voltage at the AC terminal 22 and an internal electromotive voltage of the single-phase voltage source DC/AC converting circuit 40 based on the delay single-phase alternating voltage;

(26) a power control circuit 150 which outputs a first axis voltage command value 120-1 to control amplitude of the single-phase output voltage at the AC terminal 22 and a second axis voltage command value 120-2 to control a frequency of the single-phase output voltage at the AC terminal 22 so that a DC voltage at the DC terminal 21 approaches a DC voltage command value and a reactive power value of the single-phase output power at the AC terminal 22 approaches a reactive power command value based on the DC voltage command value specifying a voltage at the DC terminal 21, the reactive power command value against the reactive power value of the single-phase output power at the AC terminal 22, a DC voltage detection value obtained by detecting a voltage at the DC terminal 21, and a reactive power measurement value of the single-phase output power at the AC terminal 22;

(27) a superior voltage control circuit 70 which outputs a voltage command signal and a frequency command signal generated so that the amplitude and the frequency of the single-phase AC output voltage at the AC terminal 22 respectively approach the first axis voltage command value 120-1 and the second axis voltage command value 120-2 based on the first axis voltage command value 120-1 and the second axis voltage command value 120-2 from the power control circuit 150, the phase difference voltage from the phase difference generating circuit 30, and the single-phase AC output at the AC terminal 22;

(28) a frequency control circuit 50 which generates a generated electrical angle based on a reference frequency of a single-phase AC output frequency at the AC terminal 22, the frequency command signal from the superior voltage control circuit 70, and the phase difference voltage from the phase difference generating circuit 30 and which synchronizes an electrical angle of an internal electromotive voltage of the single-phase source DC/AC converting circuit 40 with the generated electrical angle; and

(29) a subordinate voltage control circuit 60 which outputs a signal generated so that the amplitude, the frequency, and the phase of the single-phase output voltage approach a synthesized value of the reference voltage of the single-phase AC output voltage at the AC terminal 22, the voltage command value and the generated value as the PWM command based on the single-phase AC output voltage at the AC terminal 22, the generated value from the frequency control circuit 50, and the voltage command signal from the superior voltage control circuit 70.

(30) The first axis voltage command value 120-1 and the second axis voltage command value 120-2 correspond to the superior command vector B1 in FIG. 11. The superior voltage control circuit 70 corresponds to the superior control block B2 in FIG. 11. The subordinate voltage control circuit 60 and the frequency control circuit 50 correspond to the ac-AVR block B3 in FIG. 11. A gate signal generator 41 corresponds to the ETM-PWM block B4 in FIG. 11. A single-phase voltage source AC/DC converting unit included in the single-phase voltage source DC/AC converting circuit 40 corresponds to the main switch B5 in FIG. 11.

(31) The single-phase voltage source DC/AC converting circuit 40 converts power from the DC voltage source (not illustrated) to single-phase AC power in accordance with the pulse width of the gate signal generated by the gate signal generator 41 based on the PWM command. Examples of the DC voltage source include a voltage source such as a battery to output a DC voltage independently, a voltage source to output a DC voltage as rectifying after generating power with a power generating method such as power generation by wind, and a voltage source to output a DC voltage by controlling a voltage of a DC capacitor. Here, it is also possible that a blocking inductor is further provided between a connection point of an output voltage detecting circuit 31 and the AC terminal 22 and each single-phase AC output voltage is output from the AC terminal 22 through the blocking inductor. In this case, it is possible to prevent outflow of a PWM component to the AC terminal 22 at the single-phase voltage source DC/AC converting circuit 40.

(32) Schematic configuration diagrams of the single-phase voltage source AC/DC converting circuit are illustrated in FIGS. 7 and 8.

(33) A single-phase voltage source DC/AC converting circuit 40-1 illustrated in FIG. 7 includes a single-phase voltage source AC/DC converting unit 42 having internal equivalent impedance as seen from the AC terminal 22 to receive power from the DC voltage source at the DC terminal 21 in accordance with the pulse width of the gate signal and to output after converting to single-phase AC power, a current detecting circuit 43 which detects a single-phase AC output current of the single-phase voltage source AC/DC converting unit 42 and outputs a signal generated corresponding to magnitude of the single-phase AC output current, the gate signal generator 41 which generates and outputs the gate signal so that difference between the PWM command and the output from the current detecting circuit 43 approaches zero, and a single-phase AC filter circuit 45 which outputs as removing a high frequency component caused by the gate signal at the single-phase voltage source AC/DC converting unit 42 from the single-phase AC output voltage of the single-phase voltage source AC/DC converting unit 42.

(34) Further, instead of the current detecting circuit 43 in FIG. 7, a single-phase voltage source DC/AC converting circuit 40-2 illustrated in FIG. 8 includes a voltage detecting circuit 44 which detects a single-phase AC output voltage of the single-phase voltage source AC/DC converting unit 42 and outputs a signal generated corresponding to magnitude of the single-phase AC output voltage. In this case, the gate signal generator 41 generates and outputs the gate signal so that difference between the PWM command and the output from the voltage detecting circuit 44 approaches zero.

(35) The internal equivalent impedance included in the single-phase voltage source AC/DC converting unit 42 illustrated in FIGS. 7 and 8 can be added by control variables in the single-phase voltage source AC/DC converter 11 in FIG. 4 or by connecting a resistance, a reactor, a single-phase transformer or a combination thereof to the output of the single-phase voltage source DC/AC converting circuit 40-1, 40-2 in FIGS. 7 and 8. For example, it is possible to serially connect a resistance or a reactor to each single-phase output of the single-phase voltage source DC/AC converting circuits 40-1, 40-2. Here, in the case that a resistance is connected, it is also possible to serially connect a reactor subsequently to the resistance. Further, it is also possible to connect a single-phase transformer to a single-phase output of the single-phase voltage source DC/AC converting circuits 40-1, 40-2. Here, in the case that a reactor is connected to each single-phase output of the single-phase voltage source DC/AC converting circuits 40-1, 40-2, it is also possible to connect a single-phase transformer subsequently to the reactor. Further, in the case that a resistance is connected to each single-phase output of the single-phase voltage source DC/AC converting circuits 40-1, 40-2 and a reactor is serially connected subsequently to the resistance, it is also possible to connect a single-phase transformer subsequently to the reactor. In this manner, by allowing the single-phase voltage source DC/AC converting circuit 40 to have the internal equivalent impedance, the single-phase voltage source AC/DC converter 11 in FIG. 4 can operate as a voltage source as being connected to a power system.

(36) When the single-phase voltage source DC/AC converting circuit 40 in FIG. 4 is structured as illustrated in FIG. 7 or FIG. 8, the single-phase voltage source AC/DC converter 11 can remove a high frequency component caused by the gate signal at the single-phase voltage source AC/DC converting unit 42 from the output of the single-phase voltage source AC/DC converting unit 42 owing to being provided with the single-phase AC filter circuit 45 (as in FIGS. 7 and 8). Further, since the current or the voltage from the single-phase voltage source AC/DC converting unit 42 is detected at the current detecting circuit 43 or the voltage detecting circuit 44 and the gate signal is generated at the gate signal generator 41 so that the difference between the PWM command and the output from the current detecting circuit 43 or the voltage detecting circuit 44 approaches zero, it is possible to control current errors to be within an allowable range or to control the output voltage to follow the PWM command.

(37) The output voltage detecting circuit 31 in FIG. 4 detects the single-phase AC output voltage at the AC terminal 22 and outputs to the phase difference generating circuit 30, the subordinate voltage control circuit 60, and the superior voltage control circuit 70 respectively. Here, it is also possible that a low pass filter is arranged antecedently to the output voltage detecting circuit 31 to detect the single-phase AC output voltage to the output voltage detecting circuit 31 via the low pass filter. It is possible to stabilize control of the single-phase voltage source AC/DC converter 11 as removing the PWM component from the single-phase AC output voltage. Further, it is also possible that a low pass filter is arranged subsequently to the output voltage detecting circuit 31 to output the output voltage from the output voltage detecting circuit 31 via the low pass filter. It is possible to stabilize control of the single-phase voltage source AC/DC converter 11 as removing the PWM component from the output voltage from the output voltage detecting circuit 31.

(38) An output current detecting circuit 34 in FIG. 4 detects a single-phase AC output current at the AC terminal 22 via a current transformer 38 and outputs to an AC power measuring instrument 140.

(39) The phase difference generating circuit 30 in FIG. 4 generates the phase difference voltage corresponding to the phase difference between the single-phase AC output voltage V.sub.FIL(t) at the AC terminal 22 and the internal electromotive voltage of the single-phase voltage source DC/AC converting circuit 40. FIG. 12 illustrates an example of a schematic configuration diagram of the phase difference generating circuit 30. The phase difference generating circuit 30 includes a phase delay single-phase AC generator 35 to generate delay single-phase alternating voltage of which specified phase is delayed from single-phase AC voltage input from a terminal 33-1, a phase difference voltage generator 36 to generate the phase difference voltage from the single-phase AC voltage input from the terminal 33-1, a voltage of the delay single-phase alternating voltage from the phase delay single-phase AC generator 35 and a value input from a terminal 33-3, and a terminal 33-2 to output the phase difference voltage. In FIG. 12, the phase delay single-phase AC generator 35 delays the phase of the delay single-phase alternating voltage approximately by 90 degrees. Here, the delayed phase may be any angle as long as not being 0 degree or 180 degrees.

(40) The single-phase AC output voltage V.sub.FIL(t) detected by the output voltage detecting circuit 31 is input to the terminal 33-1. A generated electrical angle 57 generated by the later-mentioned frequency control circuit 50 is input to the terminal 33-3. The single-phase AC output voltage V.sub.FIL(t) at the AC terminal 22 is expressed by Equation 5.

(41) [Equation 5]
V.sub.FIL(t)={square root over (2)}E.sub.s.Math.sin(.sub.st+.sub.s)[V]

(42) Where, .sub.s, .sub.s, and E.sub.s respectively represent an angular frequency (rad/s), a phase angle (rad), and an effective value (V). A reference of the phase angle is based on the internal electromotive voltage.

(43) In a case that the angular frequency .sub.s of the single-phase AC output voltage at the AC terminal 22 and a reference angular frequency .sub.co of the single-phase voltage source DC/AC converting circuit 40 are equal, phase difference between the single-phase AC output voltage V.sub.FIL(t) and a phase delay single-phase AC voltage V.sub.FIL(t) becomes to 90 degrees and the phase delay single-phase AC voltage VF.sub.FIL(t) to be generated by the phase delay single-phase AC generator 35 is expressed by Equation 6.

(44) $\begin{array}{cc}\left[\mathrm{Equation}6\right]& \\ \begin{array}{c}{V}_{\mathrm{FIL}}^{}\left(t\right)=V_{\mathrm{FIL}}\left(t-\frac{}{2{}_{\mathrm{co}}}\right)=\sqrt{2}{E}_s.Math.\sin \left({}_{s}t+{}_s-\frac{{}_s}{2{}_{\mathrm{co}}}\right)\\ =-\sqrt{2}{E}_s.Math.\cos \left({}_{s}t+{}_s\right)\end{array}& \end{array}$

(45) The phase difference voltage generator 36 outputs a phase difference voltage V.sub.q(t) from the single-phase AC output voltage V.sub.FIL(t), the phase delay single-phase AC voltage V.sub.FIL(t), and the generated value generated by the frequency control circuit 50. The phase difference voltage V.sub.q(t) is expressed by Equation 7.

(46) $\begin{array}{cc}\left[\mathrm{Equation}7\right]& \\ \begin{array}{c}{V}_q\left(t\right)=V_{\mathrm{FIL}}\left(t\right).Math.\cos {}_i+V_{\mathrm{FIL}}^{}\left(t\right).Math.\sin {}_i\\ =\sqrt{2}{E}_s\left\{\sin \left({}_{s}t+{}_s-{}_i\right)+\frac{\left({}_{\mathrm{co}}-{}_s\right)}{2{}_{\mathrm{co}}}\sin \left({}_{s}t+{}_s\right)\sin {}_i\right\}\\ =\sqrt{2}{E}_s.Math.\sin \left({}_{s}t+{}_s-{}_i\right)\end{array}& \end{array}$

(47) When angular velocity of .sub.i is equal to .sub.s, Equation 3 becomes to a constant value. As being phase difference between voltages at both ends of the internal equivalent impedance, .sub.s is small generally. Accordingly, V.sub.q(t) can be approximated as Equation 8.
V.sub.q(t)={square root over (2)}E.sub.s.Math..sub.s[Equation 8]

(48) The phase difference generating circuit 30 outputs the generated phase difference voltage to the frequency control circuit 50 and the superior voltage control circuit 70 respectively. In the above, only a case that .sub.s and .sub.co are equal is described. However, even in a case of being not equal, it is possible to acquire a similar approximate solution and there is no practical problem.

(49) The frequency control circuit 50 determines the electrical angle of the internal electromotive voltage of the single-phase voltage source DC/AC converting circuit 40 based on the reference frequency of the single-phase AC output frequency at the AC terminal 22, the frequency command signal from the superior voltage control circuit 70, and the output signal from the phase difference generating circuit 30. Specifically, as illustrated in FIG. 5, a second adder 56 adds the frequency command signal from the superior voltage control circuit 70 and the phase difference voltage from the phase difference generating circuit 30. A loop filter 53 filters a low range component being a component related to the frequency difference of the single-phase AC output voltage to the frequency component of the signal output by the second adder 56. A low pass element added by the loop filter 53 is a delay element such as a primary delay element, for example. Accordingly, the feedback loop can be stabilized.

(50) Further, a third adder 58 adds the reference frequency output from a reference frequency setting unit 51 and an output value of the loop filter 53. A temporal integrator 55 performs temporal integration to the output from the third adder 58. The generated electrical angle 57 with an inherent angle .sub.i is obtained by the temporal integration on the output from the third adder 58 performed by the temporal integrator 55.

(51) The generated electrical angle 57 becomes to the electrical angle of the internal electromotive voltage of the single-phase voltage source DC/AC converting circuit 40 by a second multiplier 65 of the subordinate voltage control circuit 60. Accordingly, it is possible to allow the rotational angle to follow the frequency of the power system.

(52) Here, the phase difference generating circuit 30 outputs the phase difference voltage corresponding to the phase difference between the single-phase AC output voltage at the AC terminal 22 and the internal electromotive voltage of the single-phase voltage source DC/AC converting circuit 40 as described above. Therefore, the signal process in the phase difference generating circuit 30 is considered to correspond to the phase comparison process to compare the phases of the single-phase AC output voltage and the generated electrical angle 57 from the frequency control circuit 50. Further, the signal process to perform integration after adding the reference frequency from the reference frequency setting unit 51 and the output value from the loop filter 53 is considered to correspond to the signal process of the voltage controlled oscillator (VCO) which varies a value of the generated electrical angle 57 in accordance with the output voltage from the loop filter 53. Therefore, the phase difference generating circuit 30 and the frequency control circuit 50 are considered to perform the operation as the PLL as a whole in which the generated electrical angle 57 is synchronized with frequency of the single-phase AC output voltage at the AC terminal 22.

(53) The first axis voltage command value 120-1 and the second axis voltage command value 120-2 from the later-mentioned power control circuit 150, the generated electrical angle 57 from the frequency control circuit 50, the phase difference voltage from the phase difference generating circuit 30, and the single-phase AC output voltage at the AC terminal 22 are input to the superior voltage control circuit 70 in FIG. 4. Based on the above inputs, the superior voltage control circuit 70 outputs the voltage command signal and the frequency command signal generated so that the amplitude and the frequency of the single-phase AC output voltage at the AC terminal 22 approach the first axis voltage command value 120-1 and the second axis voltage command value 120-2. It is also possible to input the first axis voltage command value 120-1 and the second axis voltage command value 120-2 to the superior voltage control circuit 70 not directly but via a limiter 121 which defines an superior limit and a subordinate limit of the first axis voltage command value 120-1 and the second axis voltage command value 120-2. Specifically, as illustrated in FIG. 5, a first multiplier 73 multiplies a value obtained by multiplying 2 by a sine wave of the generated electrical angle 57 from the frequency control circuit 50 by the first axis voltage command value 120-1. A first subtracter 71a subtracts the AC output voltage at the AC terminal 22 from the signal from the first multiplier 73. A first superior control amplifier 72a amplifies the signal from the first subtracter 71a to output as the voltage command signal so that the single-phase AC output voltage at the AC terminal 22 approaches the first axis voltage command value 120-1. Further, a second subtracter 71b subtracts the phase difference voltage from the phase difference generating circuit 30 from a value obtained by multiplying 2 by the second axis voltage command value 120-2. A second superior control amplifier 72b amplifies the signal from the second subtracter 71b to output as the frequency command signal so that the frequency of the single-phase AC output voltage at the AC terminal 22 approaches the second axis voltage command value 120-2.

(54) Accordingly, even when the amplitude and the frequency of the power system are varied, the respective errors of the amplitude and the frequency of the single-phase output power of the single-phase voltage source AC/DC converter 11 against the amplitude and the frequency can be detected. Here, the first superior control amplifier 72a and the second superior control amplifier 72b may add the low pass element to the output from the first subtracter 71a and the second subtracter 71b. Accordingly, the feedback loop can be stabilized. Further, it is also possible to further provide the limiter subsequently to the first superior control amplifier 72a and the second superior control amplifier 72b and output the outputs from the first superior control amplifier 72a and the second superior control amplifier 72b via the limiter. It is possible to prevent the excessive output to stabilize the control.

(55) The subordinate voltage control circuit 60 in FIG. 4 outputs the signal generated so that the amplitude, the frequency, and the phase of the single-phase AC output voltage approach the synthesized value of the reference voltage of the single-phase AC output voltage at the AC terminal 22, the voltage command signal, and the electrical angle command signal as the PWM command based on the single-phase AC output voltage at the AC terminal 22, the electrical angle command signal including the generated electrical angle 57 of the frequency control circuit 50, and the voltage command signal from the superior voltage control circuit 70. Here, the reference voltage is previously set by a reference voltage setting unit 61. The reference voltage becomes to the reference of the amplitude of the single-phase AC output voltage at the AC terminal 22.

(56) Specifically, as illustrated in FIG. 5, the reference voltage setting unit 61 sets and outputs the reference voltage. The second multiplier 65 multiplies the value obtained by multiplying 2 by the sine value of the generated electrical angle 57 from the frequency control circuit 50 by the reference voltage from the reference voltage setting unit 61. A first adder 62 outputs after adding the voltage command signal from the superior voltage control circuit 70 and the signal output from the second multiplier 65. A third subtracter 63 subtracts the signal from the output voltage detecting circuit 31 from the signal output by the first adder 62. The voltage controller 64 controls the signal output by the third subtracter 63 so that the single-phase AC output voltage at the AC terminal 22 approaches the synthesized value of the reference voltage, the voltage command signal, and the electrical angle command signal to output as the PWM command.

(57) Accordingly, it is possible to compensate the error detected by the superior voltage control circuit 70 and to control the amplitude and the phase of the single-phase voltage source AC/DC converter 11 so that the amplitude and the phase of the single-phase AC output voltage of the single-phase voltage source AC/DC converter 11 is matched with the amplitude and the phase of the power system. For example, an amplifier may be adopted as the voltage controller 64. Here, it is also possible that a low pass filter is further provided between the third subtracter 63 and the voltage controller 64 and that the output from the third subtracter 63 is output via the low pass filter. It is possible to stabilize the control by the voltage controller 64. Further, it is also possible that the voltage limiter is provided between the third subtracter 63 and the voltage controller 64 (when the low pass filter is provided on this position, between the low pass filter and the voltage controller 64) and that the output from the third subtracter 63 is output via the voltage limiter. Transient variation of the output voltage at the time of activation of the single-phase voltage source AC/DC converter 11 can be inhibited.

(58) The AC power measuring instrument 140 in FIG. 4 receives inputs of the value of the single-phase AC output voltage at the AC terminal 22 detected by the output voltage detecting circuit 31 and the value of the single-phase AC output current at the AC terminal 22 detected by the output current detecting circuit 34, and then, calculates a value of active power and a value of reactive power of the single-phase output power at the AC terminal 22.

(59) Specifically, as illustrated in FIG. 9, in the AC power measuring instrument 140, a product of the voltage and the current at a power measuring point measured respectively by the output voltage detecting circuit 31 and the output current detecting circuit 34 multiplied at a multiplier 147-1 is passed through a low pass filter 149-1 and the active power value is measured at an active power value measuring circuit 145. Further, a function of which current phase at the power measuring point is shifted by 90 degrees by a current phase delaying circuit 143 is generated. Then, a product of the function and the voltage at the power measuring point multiplied at a multiplier 147-2 is passed through a low pass filter 149-2 and the reactive power value is measured by a reactive power value measuring circuit 146.

(60) Alternatively, the AC power measuring instrument 140 may be structured as illustrated in FIG. 10. The AC power measuring instrument 140 includes a reference frequency circuit 141 which generates a reference frequency, a voltage phase delaying circuit 142 which generates a delayed AC voltage as delaying the phase of the measured AC voltage being the AC voltage at the power measuring point based on the reference frequency from the reference frequency circuit 141, a current phase delaying circuit 143 which generates a delayed AC current as delaying the phase of the measured AC current being the AC current at the power measuring point based on the reference frequency from the reference frequency circuit 141, and a power arithmetic circuit 144. In the power arithmetic circuit 144, a product of the measured AC voltage and the measured AC current multiplied at the multiplier 147-1 and a product of the delayed AC voltage from the voltage phase delaying circuit 142 and the delayed AC current from the current phase delaying circuit 143 multiplied at the multiplier 147-2 are added by an adder 148-1. Then, the sum is passed through the low pass filter 149-1 to be measured as the active power value by the active power value measuring circuit 145. Further, a product of the measured AC voltage and the delayed AC current from the current phase delaying circuit 143 multiplied at a multiplier 147-3 is subtracted at a subtracter 148-2 from a product of the measured AC current and the delayed AC voltage from the voltage phase delaying circuit 142 multiplied at a multiplier 147-4. The difference is passed through a low pass filter 149-2 and the reactive power value is measured by the reactive power value measuring circuit 146. By adding the product of the delayed AC voltage and the delayed AC current to the product of the measured AC voltage and the measured AC current, a double frequency component included in the active power value can be decreased. Further, by subtracting the product of the measured AC voltage and the delayed AC current from the product of the measured AC current and the delayed AC voltage, a double frequency component included in the reactive power value can be decreased. Accordingly, the active power value and the reactive power value can be controlled accurately as improving measurement accuracy of the active power value and the reactive power value.

(61) The power control circuit 150 in FIG. 4 receives inputs of the DC voltage command value against the DC voltage at the DC terminal 21, the reactive power command value against the reactive power value of the single-phase output power at the AC terminal 22, the DC voltage detection value at the DC terminal 22 detected by a DC voltage detecting circuit 161, and the reactive power value of the single-phase output power at the AC terminal 22 calculated by the AC power measuring instrument 140. The power control circuit 150 generates and outputs the first axis voltage command value 120-1 against the amplitude of the single-phase output voltage at the AC terminal 22 and the second axis voltage command value 120-2 against the frequency thereof so that the DC voltage at the DC terminal 21 approaches the DC voltage command value and the reactive power value of the single-phase output power at the AC terminal 22 approaches the reactive power command value.

(62) FIG. 3 is a block diagram illustrating control details of the power control circuit 150. The power control circuit 150 calculates difference between the reactive power command value and the reactive power value at an adding circuit 153 and outputs the first axis voltage command value as calculating at a command value arithmetic circuit 151. Further, the power control circuit 150 calculates difference between the DC voltage command value and the DC voltage detection value at an adding circuit 154 and outputs the second axis voltage command value as calculating at a command value arithmetic circuit 152.

(63) FIGS. 13 to 15 are views illustrating arithmetic at the command value arithmetic circuit 152. The command value arithmetic circuit 152 in FIG. 13 calculates the difference between the DC voltage command value and the DC voltage detection value with a low pass characteristic circuit 152a. The low pass characteristic circuit 152a has characteristics of Equation 1.

(64) $\begin{array}{cc}\left[\mathrm{Equation}1\right]& \\ {\hat{V}}_2^{*}\left(s\right)=-\frac{K_{\mathrm{dc}}}{1+T_{\mathrm{Kdc}}.Math.s}\left({\hat{V}}_D^{*}\left(s\right)-{\hat{V}}_D\left(s\right)\right)& \left(1\right)\end{array}$

(65) where,

(66) V.sub.2* represents a second axis voltage command;

(67) V.sub.D* represents a DC voltage command value;

(68) V.sub.D represents a DC voltage detection value;

(69) s represents a variable of laplace transform;

(70) K.sub.dc represents a proportional gain;

(71) T.sub.Kdc represents a first-order lag time constant; and

(72) ^ represents a laplace transform.

(73) The command value arithmetic circuit 152 in FIG. 14 calculates the difference between the DC voltage command value and the DC voltage detection value with an integrating circuit 152b. The integrating circuit 152b has characteristics of Equation 2.

(74) $\begin{array}{cc}\left[\mathrm{Equation}2\right]& \\ {\hat{V}}_2^{*}\left(s\right)=-\frac{1}{T_{\mathrm{dc}}.Math.s}\left({\hat{V}}_D^{*}\left(s\right)-{\hat{V}}_D\left(s\right)\right)& \left(2\right)\end{array}$

(75) where,

(76) V.sub.2* represents a second axis voltage command;

(77) V.sub.D* represents a DC voltage command value;

(78) V.sub.D represents a DC voltage detection value;

(79) s represents a variable of laplace transform;

(80) T.sub.dc represents an integral time constant; and

(81) ^ represents a laplace transform.

(82) The command value arithmetic circuit 152 in FIG. 15 calculates the difference between the DC voltage command value and the DC voltage detection value with a parallel circuit 152c in which the low pass characteristic circuit 152a and the integrating circuit 152b are parallely-arranged. The parallel circuit 152c has characteristics of Equation 3.

(83) $\begin{array}{cc}\left[\mathrm{Equation}3\right]& \\ {\hat{V}}_2^{*}\left(s\right)=\left(-\frac{K_{\mathrm{dc}}}{1+T_{\mathrm{Kdc}}.Math.s}-\frac{1}{T_{\mathrm{dc}}.Math.s}\right)\left({\hat{V}}_D^{*}\left(s\right)-{\hat{V}}_D\left(s\right)\right)& \left(3\right)\end{array}$

(84) where,

(85) V.sub.2* represents a second axis voltage command;

(86) V.sub.D* represents a DC voltage command value;

(87) V.sub.D represents a DC voltage detection value;

(88) s represents a variable of laplace transform;

(89) K.sub.dc represents a proportional gain;

(90) T.sub.Kdc represents a first-order lag time constant;

(91) T.sub.dc represents an integral time constant; and

(92) ^ represents a laplace transform.

(93) Meanwhile, the command arithmetic circuit 151 in FIG. 3 calculates the difference between the reactive power command value and the reactive power value with a circuit combining a low pas filter characteristic circuit and an integrating circuit similarly to the command value arithmetic circuit 152 and generates the first axis voltage command value.

(94) For example, when the command value arithmetic circuit 151 and the command value arithmetic circuit 152 are constituted respectively with the circuit in which the low pass filter characteristic circuit and the integrating circuit are parallely-arranged, the first axis voltage command value and the second axis voltage command value are calculated with the following equation.

(95) $\begin{array}{cc}\left[\mathrm{Equation}4\right]& \\ \left(\begin{array}{c}{\hat{V}}_1^{*}\left(s\right)\\ {\hat{V}}_2^{*}\left(s\right)\end{array}\right)=\left(\begin{array}{cc}\frac{K_Q}{1+T_{\mathrm{KQ}}.Math.s}+\frac{1}{T_Q.Math.s}& 0\\ 0& -\frac{K_{\mathrm{dc}}}{1+T_{\mathrm{Kdc}}.Math.s}-\frac{1}{T_{\mathrm{dc}}.Math.s}\end{array}\right)\left(\begin{array}{c}{\hat{Q}}^{*}\left(s\right)-\hat{Q}\left(s\right)\\ {\hat{V}}_D^{*}\left(s\right)-{\hat{V}}_D\left(s\right)\end{array}\right)& \left(4\right)\end{array}$

(96) where,

(97) V.sub.1* represents a first axis voltage command (V);

(98) V.sub.2* represents a second axis voltage command (V);

(99) Q* represents a reactive power command (var);

(100) Q represents a reactive power value (var);

(101) V.sub.D* represents a DC voltage command value (V);

(102) V.sub.D represents a DC voltage detection value (V);

(103) K.sub.Q represents a first-lag gain of Q control;

(104) T.sub.KQ represents a first-order lag time constant (s) of Q control;

(105) T.sub.Q represents an integral time constant (s) of Q control;

(106) K.sub.dc represents a first-lag gain of DC voltage control;

(107) T.sub.Kdc represents a first-order lag time constant (s) of DC voltage control;

(108) T.sub.dc represents an integral time constant (s) of DC voltage control; and

(109) ^ represents a laplace transform.

(110) The single-phase voltage source AC/DC converter 11 operates as follows. When DC power is input from the DC terminal 21 side, the DC voltage detection value V.sub.D is increased. Since the error between the DC voltage detection value and the DC voltage command value V.sub.D* becomes negative, the command value arithmetic circuit 152 operates so as to increase the second axis voltage command V.sub.2*. When the DC voltage command value V.sub.D* is increased, the error against the DC voltage detection value becomes positive. Accordingly, the command value arithmetic circuit 152 operates so as to decrease the second axis voltage command V.sub.2*. In the command value arithmetic circuit 152 at the second axis voltage command V.sub.2* side, the polarity of output against input is inverted. Meanwhile, relation between the first axis voltage command V.sub.1* and the reactive power value is the same as in a case of PQ control. Accordingly, there is no inversion between input and output in the command value arithmetic circuit 151 at the first axis voltage command V.sub.1* side.

(111) The single-phase voltage source AC/DC converter 11 further includes a DC current detecting circuit 162 which detects the DC current value at the DC terminal 21. The command value arithmetic circuit 152 of the power control circuit 150 adds the DC current value detected by the DC current detecting circuit 162 to the difference between the DC voltage command value and the DC voltage detection value after the difference is calculated by the low pass characteristic circuit 152a, the integrating circuit 152b, or the parallel circuit 152c. FIGS. 16 to 18 are views illustrating arithmetic at the command value arithmetic circuit 152 in a case of adding the DC current value.

(112) FIG. 6 illustrates a schematic configuration diagram of a single-phase voltage source AC/DC converter according to another embodiment.

(113) The single-phase voltage source AC/DC converter 11 of the present embodiment in FIG. 6 includes a fourth adder 69 which further adds outputs from a filter current compensating unit 66, a PWM current deviation compensating unit 67, and a feedforward amplifier 68 to the output of the voltage controller 64 of the single-phase voltage source AC/DC converter 11 in FIG. 5. In this case, any of the single-phase voltage source DC/AC converting circuits 40-1, 40-2 illustrated in FIGS. 7 and 8 may be adopted as the single-phase voltage source DC/AC converting circuit 40. Therefore, it is assumed that either of the single-phase voltage source DC/AC converting circuits 40-1, 40-2 illustrated in FIGS. 7 and 8 is adopted in FIG. 6.

(114) The filter current compensating unit 66 outputs a current compensation value defined so as to compensate the current loss in the single-phase AC filter circuit 45 (FIGS. 7 and 8) in the single-phase voltage source DC/AC converting circuit 40. Accordingly, the single-phase voltage source AC/DC converter 11 can compensate the current loss by setting the current loss at the single-phase AC filter circuit 45 in FIG. 7 or FIG. 8 previously in the filter current compensating unit 66 and adding to the output vector from the voltage controller 64. Further, the PWM current deviation compensating unit 67 outputs a current deviation compensation value defined to compensate the current deviation of the single-phase AC output current from the single-phase voltage source DC/AC converting circuit 40. Accordingly, the single-phase voltage source AC/DC converter 11 can compensate the current deviation by setting the current deviation at the single-phase voltage source DC/AC converting circuit 40 when the PWM command is set to zero command previously in the PWM current deviation compensating unit 67 and adding to the output vector from the voltage controller 64. Further, the feedforward amplifier 68 outputs as amplifying with a predetermined feedforward gain so that the value of the single-phase AC output current detected by the output current detecting circuit 34 is input to compensate the current for the load at the AC terminal 22. Accordingly, the single-phase voltage source AC/DC converter 11 can generate the stable output voltage even when the load current is varied by detecting the single-phase AC output current at the AC terminal 22 by the output current detecting circuit 34 and adding the value to the output value from the voltage controller 64 via the feedforward amplifier 68.

(115) The limiter 121 determines the superior limit and the subordinate limit of the first axis voltage command value 120-1 and the second axis voltage command value 120-2 to prevent the first axis voltage command value 120-1 and the second axis voltage command value 120-2 from being excessively input to the superior voltage control circuit 70.

(116) As described above, the single-phase voltage source AC/DC converter 11 in FIGS. 4 to 6 is capable of performing autonomous parallel operation as autonomously compensating the power deviation against the power system owing to including the frequency control circuit 50, the superior voltage control circuit 70, and the subordinate voltage control circuit 60, while being capable of performing operation as being connected to the power system as the voltage source owing to having the internal equivalent impedance. Accordingly, reliability of the device is improved and dispersed arrangement can be adopted. In addition, in a case of parallel operation with a plurality of devices, it is possible to perform the operation without limitation in the number of the devices.

(117) Further, since the power control circuit 150 includes the command value arithmetic circuit 152 and the second axis voltage command is generated in accordance with the DC voltage detection value, the single-phase voltage source AC/DC converter 11 can maintain the DC voltage at the DC terminal 21 at constant. Accordingly, the single-phase source AC/DC converter 11 is capable of performing autonomous parallel operation while being capable of connecting a DC device of which outputting or requiring DC power fluctuates to the DC terminal 21.

(118) [Interconnection System]

(119) Next, an interconnection system 301 including the single-phase voltage source AC/DC converter 11 illustrated in FIGS. 4 to 6 is described. FIG. 19 is a view illustrating a configuration of the interconnection system 301. The interconnection system 301 includes the single-phase voltage source AC/DC converter 11 and n (n is any positive integer) sets of DC devices 203 which are connected to the DC terminal 21 of the single-phase voltage source AC/DC converter 11 via a DC/DC converters 202 and which performs transmitting and receiving of DC power with the DC terminal 21.

(120) The DC/DC converter 202 is a DC converter of a current output type. For example, when the DC device 203 is a solar cell, the DC/DC converter 202 adjusts a voltage and a current so as to obtain the maximum power from the solar cell.

(121) The DC device 203 is a DC energy source or a DC load. The DC energy source denotes a solar cell, a secondary cell, a fuel battery and the like, for example. The DC load denotes a battery charger, for example. In the interconnection system 301, since the single-phase voltage source AC/DC converter 11 can maintain the DC voltage at the DC terminal 21 at constant, the DC device 203 can be connected directly to the DC terminal 21 via the DC/DC converter 202.

(122) Here, in addition to transmitting and receiving of power between the DC device 203 and the power system, it is also possible that DC power is directly supplied to the DC device 203 being the DC load from the DC device 203 being the DC energy source in the interconnection system 301. Since the single-phase voltage source AC/DC converter 11 operates so as to maintain the DC voltage at the DC terminal 21 at a constant value even when the DC voltage from the DC energy source fluctuates, the DC load can receive power at a constant voltage.

EXAMPLE

(123) FIG. 20 shows a simulation result with a single-phase voltage source AC/DC converter at 200 V, 50 Hz, and 1 kVA. The single-phase voltage source AC/DC converter includes the circuit in FIG. 4 as the command value arithmetic circuit in the power control circuit. Then, the DC voltage command value to be input to the power control circuit is set to 330 V. Control parameters are set as K.sub.dc=0.6, T.sub.dc=2 ms, and T.sub.Kdc=0.25 sec. Interconnection operation was performed in a state of no load at the DC side in the beginning, and then, 1 kW of step-shaped DC load was applied at time 160 ms. The DC voltage at the DC terminal 21 was decreased by 30 V after the load was applied. However, power immediately inflew from the AC terminal 22 side via the single-phase voltage source DC/AC converting circuit 40, so that the DC voltage returned approximately to the DC voltage command value at time 200 ms. Here, the receiving current waveform from the power system formed a sine wave as the power factor being 1.

(124) The single-phase voltage source AC/DC converter of the present invention can be applied for an inverter for a dispersed power source such as a solar power generation inverter, a fuel cell inverter, a storage system inverter and a wind power generation inverter with a DC link, a rectifier, a static var compensator (SVC), and the like.

DESCRIPTION OF REFERENCE NUMERALS

(125) 11: single-phase voltage source AC/DC converter 21: DC terminal 22: AC terminal 30: phase difference generating circuit 31: output voltage detecting circuit 33-133-3: terminal 34: output current detecting circuit 35: phase delay single-phase AC generator 36: phase difference voltage generator 38: current transformer 40: single-phase voltage source DC/AC converting circuit 40-1, 40-2: single-phase voltage source DC/AC converting circuit 41: gate signal generator 42: single-phase voltage source AC/DC converting unit 43: current detecting circuit 44: voltage detecting circuit 45: single-phase AC filter circuit 50: frequency control circuit 51: reference frequency setting unit 53: loop filter 55: temporal integrator 56: second adder 57: generated electrical angle 58: third adder 60: subordinate voltage control circuit 61: reference voltage setting unit 62: first adder 63: third subtracter 64: voltage controller 65: second multiplier 66: filter current compensating unit 67: PWM current deviation compensating unit 68: feedforward amplifier 69: fourth adder 70: superior voltage control circuit 71a: first subtracter 71b: second subtracter 72a: first superior control amplifier 72b: second superior control amplifier 73: first multiplier 120-1: first axis voltage command value 120-2: second axis voltage command value 121: limiter 140: AC power measuring instrument 141: reference frequency circuit 142: voltage phase delaying circuit 143: current phase delaying circuit 144: power arithmetic circuit 145: active power value measuring circuit 146: reactive power value measuring circuit 147-1, 147-2, 147-3, 147-4: multiplier 148-1: adder 148-2: subtracter 149-1, 149-2: low pass filter 150: power control circuit 151: command value arithmetic circuit 152: command value arithmetic circuit 152a: low pass characteristic circuit 152b: integrating circuit 152c: parallel circuit 153: adding circuit 154: adding circuit 161: DC voltage detecting circuit 162: DC current detecting circuit 202: DC/DC converter 203: DC device 301: inter connection system B1: superior command vector B2: superior control block B3: ac-AVR block B4: ETM-PWM block B5: main switch