Abstract
Disclosed is a high step down power converter. The power converter includes a bridge circuit and a chain of transformer-rectifier (TR) blocks. Each of the TR blocks has a transformer and a rectifier circuit. The transformer has a magnetic core, primary windings that have one or more turns, and secondary windings that are wound a single turn over corresponding primary windings. The bridge circuit is driven to generate a primary winding current, which flows to the primary windings of the transformers of the TR blocks. Currents induced in the secondary windings are rectified by the rectifier circuits to generate an output current that is provided to a load that is connected to the power converter.
Claims
1. A power converter comprising: a bridge circuit; and a chain of transformer-rectifier (TR) blocks, each of the TR blocks comprising a transformer and a rectifier circuit, a first end of a first primary winding of the transformer is connected to a first node of the TR block, a second end of the first primary winding is connected to a first end of a second primary winding of the transformer, a second end of the second primary winding is connected to a second node of the TR block, a first end of a first secondary winding of the transformer is connected to a first end of a first rectifier of the rectifier circuit, a second end of the first secondary winding is connected to a first end of a second secondary winding of the transformer, a second end of the second secondary winding is connected to a first end of a second rectifier of the rectifier circuit, the second end of the first secondary winding and the first end of the second secondary winding are connected to a third node of the TR block; wherein primary windings of transformers of TR blocks of the chain of TR blocks are connected in series to the bridge circuit, and third nodes of the TR blocks of the chain of TR blocks deliver an output current to a load that is connected to the power converter.
2. The power converter of claim 1, wherein a coefficient of coupling between the first and second secondary windings is greater than zero.
3. The power converter of claim 2, wherein the transformer of each of the TR blocks comprises a magnetic core, the first primary winding is wound one or more turns around a first yoke of the magnetic core between a first leg of the magnetic core and a second leg of the magnetic core, the first secondary winding is wound a single turn over the first primary winding around the first yoke, the second primary winding is wound one or more turns around a second yoke of the magnetic core between the second leg and a third leg of the magnetic core, and the second secondary winding is wound a single turn over the second primary winding around the second yoke, and the first and second yokes are along a long side of the magnetic core.
4. The power converter of claim 3, wherein there is a gap between the second leg and the second yoke.
5. The power converter of claim 1, wherein the magnetic core is a single piece magnetic core.
6. The power converter of claim 1, wherein the magnetic core is a multipiece magnetic core.
7. The power converter of claim 1, wherein the coefficient of coupling between the first and second secondary windings is less than zero.
8. The power converter of claim 7, wherein the transformer of each of the TR blocks comprises a magnetic core, the first primary winding is wound one or more turns around a first yoke of the magnetic core between a first leg of the magnetic core and a second leg of the magnetic core, the first secondary winding is wound a single turn over the first primary winding around the first yoke, the second primary winding is wound one or more turns around the first yoke between the second leg and a third leg of the magnetic core, and the second secondary winding is wound a single turn over the second primary winding around the first yoke.
9. The power converter of claim 8, wherein there is a gap between the first leg and a second yoke of the magnetic core, there is a gap between the third leg and the second yoke, and the first and second yokes are along a long side of the magnetic core.
10. The power converter of claim 1, wherein the bridge circuit is a half bridge circuit.
11. The power converter of claim 1, wherein the bridge circuit is a full bridge circuit.
12. A method of operation of a power converter, the method comprising: driving a bridge circuit by pulse width modulation (PWM) to generate a primary winding current that flows from the bridge circuit; flowing the primary winding current from the bridge circuit to a plurality of primary windings that are connected in series, the primary winding current inducing a plurality of secondary winding currents in a plurality of secondary windings that are magnetically coupled to corresponding primary windings of the plurality of primary windings; and rectifying the plurality of secondary winding currents to generate a plurality of output currents that are provided to a load of the power converter.
13. The method of claim 12, wherein the bridge circuit is a full bridge circuit that is driven by symmetric PWM control signals.
14. The method of claim 12, wherein the bridge circuit is a full bridge circuit that is driven by phase shifted PWM control signals.
15. The method of claim 12, wherein the bridge circuit is a half bridge circuit that is driven by symmetric PWM control signals.
16. The method of claim 12, wherein the bridge circuit is a half bridge circuit that is driven by asymmetric PWM control signals.
Description
BRIEF DESCRIPTION OF THE DRAWINGS
[0005] A more complete understanding of the subject matter may be derived by referring to the detailed description and claims when considered in conjunction with the following figures, wherein like reference numbers refer to similar elements throughout the figures.
[0006] FIG. 1 shows a block diagram of a high step down power converter, in accordance with an embodiment of the present invention.
[0007] FIG. 2 shows a schematic diagram of a high-voltage half bridge circuit, in accordance with an embodiment of the present invention.
[0008] FIG. 3 shows a schematic diagram of a high-voltage full bridge circuit, in accordance with an embodiment of the present invention.
[0009] FIG. 4 shows a schematic diagram of a transformer-rectifier (TR) block, in accordance with an embodiment of the present invention.
[0010] FIG. 5 shows a schematic diagram of a TR block, in accordance with an embodiment of the present invention.
[0011] FIGS. 6-9 show various views of a transformer of the TR block of FIG. 5, where each of the primary windings has a single turn, in accordance with an embodiment of the present invention.
[0012] FIGS. 10-12 show various views of a transformer of the TR block of FIG. 5, where each of the primary windings has a plurality of turns, in accordance with an embodiment of the present invention.
[0013] FIG. 13 shows a schematic diagram of a TR block, in accordance with an embodiment of the present invention.
[0014] FIGS. 14-16 show various views of a transformer of the TR block of FIG. 13, in accordance with an embodiment of the present invention.
[0015] FIG. 17 shows a schematic diagram of a high step down power converter, in accordance with an embodiment of the present invention.
[0016] FIGS. 18 and 19 show timing diagrams of the power converter of FIG. 17, in accordance with an embodiment of the present invention.
[0017] FIG. 20 shows a schematic diagram of a power converter, in accordance with an embodiment of the present invention.
[0018] FIGS. 21 and 22 show timing diagrams of the power converter of FIG. 20, in accordance with an embodiment of the present invention.
[0019] FIG. 23 shows a top view of a TR block, in accordance with an embodiment of the present invention.
[0020] FIG. 24 shows a top view of a transformer module of the TR block of FIG. 23, in accordance with an embodiment of the present invention.
[0021] FIG. 25 shows a top view of a TR block, in accordance with an embodiment of the present invention.
[0022] FIG. 26 shows a top view of horizontally disposed TR blocks, in accordance with an embodiment of the present invention.
[0023] FIG. 27 shows a front view of a TR block, in accordance with an embodiment of the present invention.
[0024] FIG. 28 shows a top view of a rectifier module of the TR block of FIG. 27, in accordance with an embodiment of the present invention.
[0025] FIG. 29 shows a top view of a bottom surface of a transformer module of the TR block of FIG. 27, in accordance with an embodiment of the present invention.
[0026] FIG. 30 shows a top view of a transformer module of the TR block of FIG. 27, in accordance with an embodiment of the present invention.
[0027] FIGS. 31 and 32 show front views of the TR block of FIG. 27, in accordance with an embodiment of the present invention.
[0028] FIG. 33 shows a top view of TR blocks, in accordance with an embodiment of the present invention.
DETAILED DESCRIPTION
[0029] In the present disclosure, numerous specific details are provided, such as examples of circuits, components, structures, materials, and methods, to provide a thorough understanding of embodiments of the invention. Persons of ordinary skill in the art will recognize, however, that the invention can be practiced without one or more of the specific details. In other instances, well-known details are not shown or described to avoid obscuring aspects of the invention.
[0030] FIG. 1 shows a block diagram of a high step down step down power converter 100, in accordance with an embodiment of the present invention. The power converter 100 converts a DC input voltage VIN to a regulated DC output voltage VOUT. The power converter 100 is a high step down power converter in that the ratio of the input voltage VIN to the output voltage VOUT is relatively high. In one embodiment, the input voltage VIN is 48V and the output voltage VOUT is 1V. The output voltage VOUT is developed across a load, which is represented by a load resistor R.sub.LOAD. The load may be a Graphics Processing Unit (GPU), Central Processing Unit (CPU), or other electrical circuit. An output capacitor Cour is across the load resistor R.sub.LOAD.
[0031] In the example of FIG. 1, the power converter 100 comprises a high-voltage bridge circuit 110 and a plurality of transformer-rectifier blocks (TR) 120 (i.e., 120-1, 120-2, . . . , 120-M). The bridge circuit 110 may be a half bridge circuit or full bridge circuit. A TR block 120 comprises a transformer and a rectifier circuit. The transformer and the rectifier circuit may be implemented as a single, integrated module or as separate, discrete modules (e.g., as a transformer module and a separate rectifier circuit module). A transformer module or rectifier module is a self-contained discrete unit that can be easily integrated into a more complex system, such as a power supply. A transformer module and a rectifier module may be disposed horizontally side by side on a substrate or disposed vertically one on top of the other.
[0032] The power converter 100 is scalable in that TR blocks 120 may be added to or removed from the power converter 100 to meet the requirements of a specific application. In the example of FIG. 1, the TR blocks 120 are connected to provide the output voltage VOUT. TR blocks 120 may be added or removed to increase or decrease the output current IOUT of the power converter 100.
[0033] In the example of FIG. 1, a TR block 120 includes a node 1 that is connected to one end of a primary winding of a transformer, a node 2 that is connected to the output voltage VOUT, a node 3 that is connected to ground, and a node 4 that is connected to the other end of the primary winding of the transformer. The primary windings of the transformers of the TR blocks 120 are connected in series by connecting a node 4 of a TR block 120 to a node 1 of the next TR block 120 to form a chain of TR blocks 120.
[0034] In the example of FIG. 1, the bridge circuit 110 includes a node 11 that receives the input voltage VIN, a node 12 that is connected to ground, a node 13 that is connected to a node 4 of a TR block 120 at one end of the chain of TR blocks, and a node 14 that is connected to a node 1 of a TR block 120 at the other end of the chain of TR blocks. The ground of the bridge circuit 110 (at node 12) and the ground of the TR blocks 120 (at node 3) may be tied together or isolated depending on the application.
[0035] In the example of FIG. 1, the bridge circuit 110 converts the DC input voltage VIN to an AC current i.sub.Lp that flows directly to the TR block 120-1, instead of to an intermediate circuit stage between the half bridge circuit 110 and the TR blocks 120. This design eliminates the need to develop an intermediate bus voltage, thereby reducing parts count by removing the bus voltage capacitor and transistors of the intermediate circuit stage. The current i.sub.Lp from the bridge circuit 110 flows to the series-connected primary windings of transformers of the TR blocks 120. Currents induced in the secondary windings of the transformers are rectified by corresponding TR blocks 120 to generate rectified output currents i.sub.LOUT (i.e., i.sub.LOUT1, i.sub.LOUT2, . . . , i.sub.LOUTM) that flow to the load. The rectified output currents i.sub.LOUT of the TR blocks 120 collectively form the output current IOUT of the power converter 100, which is delivered to the load.
[0036] FIG. 2 shows a schematic diagram of a high-voltage half bridge circuit 110A, in accordance with an embodiment of the present invention. The bridge circuit 110A is a half bridge embodiment of the bridge circuit 110 of FIG. 1. In the example of FIG. 2, the half bridge circuit 110A comprises a switch S1, a switch S2, and a capacitor C1. The switch S1 has a first end that is connected to the node 11 and a second end that is connected to a first end of the switch S2. The current i.sub.Lp flows from a bridge node that is formed by the second end of the switch S1 and the first end of the switch S2 at the node 14. The capacitor C1 has a first end that is connected to the node 13 and a second end that is connected to ground at the node 12.
[0037] FIG. 3 shows a schematic diagram of a high-voltage full bridge circuit 110B, in accordance with an embodiment of the present invention. The bridge circuit 110B is a full bridge embodiment of the bridge circuit 110 of FIG. 1. In the example of FIG. 3, the full bridge circuit 110B comprises switches S3-S6. The switch S3 has a first end that is connected to the node 11 and a second end that is connected to a first end of the switch S4. The switch S4 has a second end that is connected to ground at the node 12. The switch S5 has a first end that is connected to the node 11 and a second end that is connected to a first end of the switch S6. The switch S6 has a second end that is connected to ground at the node 12. The second end of the switch S3 and the first end of the switch S4 form a first bridge node at the node 14, from which the current i.sub.Lp flows. The second end of the switch S5 and the first end of the switch S6 form a second bridge node that is connected to the node 13.
[0038] In the example of FIGS. 2 and 3, each of the switches S1-S6 is a Metal-Oxide-Semiconductor Field-Effect Transistor (MOSFET), the first end of each of the switches S1-S6 is a drain, and the second end of each of the switches S1-S6 is a source. A control end of each of the switches S1-S6 is a gate, which may receive a corresponding signal in accordance with a control scheme (e.g., pulse width modulation (PWM)) to control the operation of the power converter 100 of FIG. 1 to generate a regulated output voltage VOUT. As can be appreciated other suitable types of transistors may also be employed.
[0039] FIG. 4 shows a schematic diagram of a TR block 120, in accordance with an embodiment of the present invention. In one embodiment, the TR block 120 comprises a transformer T1 and a rectifier circuit 130. The transformer T1 has primary windings L11 and L12 and secondary windings L21 and L22. The primary windings L11 and L12 are connected in series. Each of the windings L11, L12, L21, and L22 may comprise a flat copper wire, for example. The current i.sub.Lp from the bridge circuit 110 or previous TR block 120 in a chain of TR blocks 120 enters the node 1, flows to the primary windings L11 and L12, and exits to flow to the bridge circuit 110 or next TR block 120 in the chain of TR blocks 120.
[0040] In one embodiment, the turns ratio between the primary and secondary windings is N:1. That is, the primary winding L11 has N turns and the corresponding secondary winding L21 has 1 turn. Similarly, the primary winding L12 has N turns and the corresponding secondary winding L22 has 1 turn. The phase relationships between voltage and current in the primary winding L11 and secondary winding L21 and in the primary winding L12 and secondary winding L22 are as per the dot convention shown in FIG. 4.
[0041] In the example of FIG. 4, K12 is the coefficient of coupling between the primary winding L11 and the secondary winding L21; K21 is the coefficient of coupling between the primary winding L12 and the secondary winding L22; K11 is the coefficient of coupling between the primary windings L11 and L12; and K22 is the coefficient of coupling between the secondary windings L21 and L22. The relationships between the coupling coefficients are,
[00001]
[0042] The primary winding L11 has a first end that is connected to the node 1 and a second end that is connected to a first end of the primary winding L12.
[0043] In the example of FIG. 4, the rectifier circuit 130 comprises a rectifier 121 and a rectifier 122. Each of the rectifiers 121 and 122 may comprise a MOSFET or other switch. The rectifiers 121 and 122 are configured as synchronous rectifiers, but are represented by their body diodes in FIG. 4 for case of illustration. The secondary winding L21 has a first end that is connected to a first end of the rectifier 121 and a second end that is connected to a first end of the secondary winding L22. The second end of the secondary winding L22 is connected to a first end of the rectifier 122. The second end of the secondary winding L21 and the first end of the secondary winding L22 form a rectifier output node that is connected to the node 2. The second ends of the rectifiers 121 and 122 are both connected to the node 3. The output current i.sub.LOUT of the rectifier 120 flows to the load by way of the node 2.
[0044] FIG. 5 shows a schematic diagram of a TR block 120A, in accordance with an embodiment of the present invention. The TR block 120A is a particular embodiment of the TR block 120 of FIG. 4 where,
[00002]
[0045] The TR block 120A comprises the transformer T1 and the rectifier circuit 130. In the example of FIG. 5, the transformer T1 comprises the primary windings L11 and L12, secondary windings L21 and L22, and a magnetic core 210.
[0046] In the example of FIG. 5, the magnetic core 210 has a plurality of bar portions that are arranged in rectangular fashion comprising legs 230-232 that are along the short side, and yokes 240 and 241 that are along the long side. The legs 230 and 232 are connected to both of the opposing yokes 240 and 241. The leg 231, which is between the legs 230 and 231, is connected only to one of the yokes (the yoke 241). In other words, there is an air gap 233 between the leg 231 and the yoke 240. The air gap 233 help prevent saturation. Small gaps may also exist in yokes 240 and 241 and in legs 230 and 232 to avoid saturation; however these gaps are shorter than the air gap 233.
[0047] The magnetic core 210 may be a single-piece or multipiece core that is made of a magnetic material that is commonly-used in magnetic cores. For example, the yoke 240, yoke 241, leg 230, leg 231, and leg 232 may be made of a single piece of magnetic material. As another example, one or more of the yokes 240, yoke 241, leg 230, leg 231, and leg 232 may be separate pieces of magnetic material.
[0048] In the example of FIG. 5, the primary winding L12 (depicted as a dash line) starts at the node 4, winds around the yoke 240 between the legs 230 and 231 one or more turns, then goes under the yoke 241 to form the primary winding L11. The primary winding L11 winds around the yoke 241 between the legs 231 and 232 one or more turns, then connects to the node 1. The secondary winding L21 starts at the first end (cathode in FIG. 5) of the rectifier 122, goes over the yoke 241 to make a single turn around the yoke 241, and goes under the yoke 240 to connect to the node 2. The secondary winding L22 starts at the first end (cathode in FIG. 5) of the rectifier 121, goes under the yoke 241, and goes over the yoke 240 to wind a single turn around the yoke 240 to connect to the node 2. The second ends (anode in FIG. 5) of the rectifiers 121 and 122 are connected to the node 3.
[0049] In the example of FIG. 5, it is to be noted that the primary winding L11 and the secondary winding L21 wind around the yoke 241, whereas the primary winding L12 and the secondary winding L22 wind around the yoke 240. That is, the primary/secondary winding pairs wind around opposing yokes.
[0050] FIGS. 6-9 show various views of the transformer T1, where each of the primary windings L11 and L12 has a single turn, in accordance with an embodiment of the present invention. In the example of FIGS. 6-9, each of the primary windings L11 and L12 is wound 1 turn, and each of the secondary windings L21 and L22 is wound 1 turn. In the example of FIGS. 6-9, the primary winding L11, primary winding L12, secondary winding L21, and secondary winding L22 are flat copper wires with enamel coating and have the same widths. Generally, primary and secondary windings disclosed herein may be insulated using materials or insulation structures that are available in the transformer industry.
[0051] FIG. 6 shows a perspective view of the transformer T1. To improve heat dissipation, the secondary winding L21 is wound over the primary winding L11 and the secondary winding L22 is wound over the primary winding L12. FIG. 7 shows a side view of the primary winding L11 and the secondary winding L21. FIG. 8 shows a side view of the primary winding L12 and the secondary winding L22. FIG. 9 shows a top view of the magnetic core 210, illustrating the air gap 233 between the leg 231 and a yoke of the magnetic core 210.
[0052] FIGS. 10-12 show various views of the transformer T1, where each of the primary windings L11 and L12 has a plurality of turns, in accordance with an embodiment of the present invention. In the example of FIGS. 10-12, each of the primary windings L11 and L12 is wound a plurality of turns, and each of the secondary windings L21 and L22 is wound 1 turn. In the example of FIGS. 10-12, the primary winding L11, primary winding L12, secondary winding L21, and secondary winding L22 are flat copper wires with enamel coating, and the primary windings L11 and L12 are narrower than the secondary windings L21 and L22.
[0053] FIG. 10 shows a perspective view of the transformer T1. As before, the secondary winding L21 is wound over the primary winding L11 and the secondary winding L22 is wound over the primary winding L12 to improve heat dissipation.
[0054] FIG. 11 shows a perspective view of the primary winding L11 and the secondary winding L21, and FIG. 12 shows a perspective view of the primary winding L12 and the secondary winding L22. FIGS. 11 and 12 illustrate the multiple turns of the primary windings L11 and L12, which are narrower than the secondary windings L21 and L22, respectively.
[0055] FIG. 13 shows a schematic diagram of a TR block 120B, in accordance with an embodiment of the present invention. The TR block 120B is a particular embodiment of the TR block 120 of FIG. 4 where,
[00003]
[0056] The TR block 120B comprises a transformer T2 and the rectifier circuit 130. The transformer T2 is a particular embodiment of the transformer T1. The transformer T2 comprises the primary windings L11 and L12, secondary windings L21 and L22, and a magnetic core 211.
[0057] Similar to the magnetic core 210 of the transformer T1, the magnetic core 211 has a plurality of bar portions that are arranged in rectangular fashion comprising legs 230-232 on the short side, and yokes 240 and 241 on the long side. In the case of the magnetic core 211, the leg 231 is connected to both of the opposing yokes 240 and 241, whereas each of the legs 230 and 232 is connected only to one yoke. In the magnetic core 211, there is an air gap 224 between the leg 230 and the yoke 240, and there is an air gap 225 between the leg 232 and the yoke 240. The air gaps 224 and 225 help prevent saturation.
[0058] The magnetic core 211 may be a single-piece or multipiece core that is made of a magnetic material that is commonly-used in magnetic cores. For example, the yoke 240, yoke 241, leg 230, leg 231, and leg 232 may be made of a single piece of magnetic material. As another example, one or more of the yoke 240, yoke 241, leg 230, leg 231, and leg 232 may be separate pieces of magnetic material.
[0059] In the example of FIG. 13, the primary winding L11 (depicted as a dash line) starts at the node 1, winds around the yoke 241 between the legs 230 and 231 one or more turns, goes under the leg 231, then goes over the yoke 241 to form the primary winding L12. The primary winding L12 winds around the yoke 241 between the legs 231 and 232 one or more turns, then connects to the node 4. The secondary winding L21 starts at the first end (cathode in the example of FIG. 13) of the rectifier 121, goes over the yoke 241 to wound a single turn around the yoke 241, then goes under the yoke 240 to connect to the node 2. The secondary winding L22 starts at the first end (cathode in the example of FIG. 13) of the rectifier 122, goes over the yoke 241 to wind around the yoke 241 a single turn, then goes under the yoke 240 to connect to the node 2. The second ends (anode in the example of FIG. 13) of the rectifiers 121 and 122 are connected to the node 3.
[0060] In the example of FIG. 13, it is to be noted that the primary winding L11, the secondary winding L21, the primary winding L12, and the secondary winding L22 wind around the yoke 241. That is, all of the primary/secondary winding pairs wind around the same yoke. This is in contrast to the example of FIG. 5, where the primary/secondary winding pairs wind around opposing yokes.
[0061] FIGS. 14-16 show various views of the transformer T2, in accordance with an embodiment of the present invention. In the example of FIGS. 14-16, each of the primary windings L11 and L12 is wound 1 turn, and each of the secondary windings L21 and L22 is wound 1 turn. In the example of FIGS. 14-16, the primary winding L11, primary winding L12, secondary winding L21, and secondary winding L22 are flat copper wires with enamel coating and have the same widths.
[0062] FIG. 14 shows a perspective view of the transformer T2. To improve heat dissipation, the secondary winding L21 is wound over the primary winding L11 and the secondary winding L22 is wound over the primary winding L12. FIG. 15 shows a side view that illustrates the secondary winding L21/L22 over the primary winding L11/L12. FIG. 16 shows a top view of the magnetic core 211, which illustrates the air gap 224 between the leg 230 and the yoke 240 and the air gap 225 between the leg 232 and the yoke 240. In the magnetic core 211, only the leg 231 is connected to both of the opposing yokes. An air gap may also exist between the leg 231 and the yoke 240, but its gap length is narrower than that of the air gaps 224 and 225.
[0063] FIG. 17 shows a schematic diagram of the power converter 100, in accordance with an embodiment of the present invention. FIG. 17 illustrates a particular embodiment of the power converter 100 of FIG. 1. In the example of FIG. 17, the power converter 120 comprises the half bridge circuit 110A (also shown in FIG. 2) and a plurality of TR blocks 120. The nodes 11-14 of the half bridge circuit 110A and the nodes 1-4 of each of the TR blocks 120 are connected as in FIG. 1.
[0064] In the example of FIG. 17, a PWM controller 301 generates a PWM_H signal that is provided to the control end of the switch S1 and a PWM_L signal that is provided to the control end of the switch S2. The PWM controller 301 may generate the PWM_H and PWM_L signals in accordance with a suitable PWM control scheme, such as by symmetric half bridge control (SHB) or asymmetric half bridge (AHB) control.
[0065] The following signals are shown in FIG. 17: (a) a current i.sub.MH flowing from the node 11 to the node 14 through the switch S1; (b) the current i.sub.Lp flowing from the node 14 to the node 1 of the TR block 120-1; (c) a current i.sub.ML flowing through the switch S2 to ground; and (d) an output current IOUT flowing to the load represented by the resistor R.sub.LOAD. Note that in the example of FIG. 17, the current i.sub.Lp flows directly to the TR block 120-1, instead of to an intermediate circuit stage between the half bridge circuit 110A and the TR block 120-1.
[0066] FIG. 17 further shows the following signals that are in each TR block 120: (a) a voltage Vswa between a first end of the secondary winding L21 and a first end of the rectifier 121; (b) a current i.sub.D1 flowing to the secondary winding L21 through the rectifier 121; (c) a voltage Vswb between a second end of the secondary winding L22 and a first end of the rectifier 122; a current i.sub.D2 flowing to the secondary winding L22 through the rectifier 122; and a current i.sub.LOUT flowing to the load. Note that the output currents i.sub.LOUT of the TR blocks 120 (i.e., i.sub.LOUT1, . . . , i.sub.LOUTM) add up to provide the overall output current IOUT of the power converter 100.
[0067] FIG. 18 shows a timing diagram of the power converter 100, in accordance with an embodiment of the present invention. In the example of FIG. 18, the circled numbers on top of the diagram represent repeated phases, and the horizontal axis represents time.
[0068] In the example of FIG. 18, the PWM controller 301 generates the control signals PWM_H and PWM_L in accordance with a symmetric half bridge control scheme. The control signals PWM_H and PWM_L are symmetric in that they have the same duty cycle or ON time, and have 180 degree phase shift. The signals shown in FIG. 18 are shown in FIG. 17 and include those of the TR block 120-1. The signals for the other TR blocks 120 are essentially the same as in the TR block 120-1. For convenience of the reader, the current i.sub.LOUT is also labeled as 311, the current i.sub.D1 is also labeled as 312, the current i.sub.MH is also labeled as 313, and the current i.sub.ML is also labeled as 314.
[0069] For symmetric half bridge control as in the example of FIG. 18, the output voltage VOUT of the power converter 100 is given by:
[00004] [0070] where D is the duty cycle of the control signals PWM_H and PWM_L, VIN is the input voltage, N is the number of turns of the primary windings L11 and L12, and M is the number of TR blocks 120.
[0071] In an example operation, referring to FIGS. 17 and 18, the DC input voltage VIN is received by the half bridge circuit 110A. The half bridge circuit 110A is driven by pulse width modulation (PWM) (see PWM_H, PWM_L) to generate a primary winding current (see current i.sub.Lp). The primary winding current flows from the half bridge circuit 110A to a plurality of primary windings that are connected in series. The primary winding current induces a plurality of secondary winding currents in a plurality of secondary windings that are magnetically coupled to corresponding primary windings of the plurality of primary windings. The plurality of secondary winding currents are rectified to generate a plurality of output currents (see output current i.sub.LOUT) that are provided to a load of the power converter (see output current IOUT).
[0072] FIG. 19 shows a timing diagram of the power converter 100, in accordance with an embodiment of the present invention. In the example of FIG. 19, the circled numbers on top of the diagram represent repeated phases and the horizontal axis represents time.
[0073] In the example of FIG. 19, the PWM controller 301 generates the control signals PWM_H and PWM_L in accordance with an asymmetric half bridge control scheme. The control signals PWM_H and PWM_L are asymmetric in that they have different duty cycles and their currents i.sub.MH and i.sub.ML are different; in the example of FIG. 19, the control signals PWM_H and PWM_L are complementary. The signals shown in FIG. 19 are as shown in FIG. 17 and include those of the TR block 120-1. The signals for the other TR blocks 120 are essentially the same as in the TR block 120-1. For convenience of the reader, the current i.sub.LOUT1 is also labeled as 411, the current i.sub.D1 is also labeled as 410, and the current i.sub.D2 is also labeled as 412. The arrows ZCS indicate points of zero-current switching, and the arrows ZVS indicate points of zero-voltage switching.
[0074] For asymmetric half bridge control as in the example of FIG. 19, the output voltage VOUT of the power converter 100 is given by:
[00005]
where D is the duty cycle of the control signals PWM_H and PWM_L, VIN is the input voltage, N is the number of turns of the primary windings L11 and L12, and M is the number of TR blocks 120.
[0075] The operation of the power converter 100 in the case of FIG. 19 is similar to that in the case of FIG. 18, except for some variations that are due to the symmetric half bridge PWM control of the half bridge circuit 110A. The processing of the input voltage VIN by the half bridge circuit 110A, generation of the primary winding current by the half bridge circuit 110A, flowing of the primary winding current from the half bridge circuit 110A to the primary windings to induce secondary winding currents in the secondary windings, and rectifying the secondary winding currents to generate output currents that are provided to the load of the power converter 100 are similar to those in the example of FIG. 18.
[0076] FIG. 20 shows a schematic diagram of the power converter 100, in accordance with an embodiment of the present invention. FIG. 20 illustrates a particular embodiment of the power converter 100 of FIG. 1. In the example of FIG. 20, the power converter 120 comprises the full bridge circuit 110B (also shown in FIG. 3) and a plurality of TR blocks 120. The nodes 11-14 of the full bridge circuit 110B and the nodes 1-4 of the TR blocks 120 are connected as in FIG. 1. The signals shown in FIG. 20 are as described with reference to FIG. 17, except that the current i.sub.MH flows to the node 14 through the switch S3 (instead of through the switch S1) and the current i.sub.ML flows to ground through the switch S4 (instead of through the switch S2).
[0077] In the example of FIG. 20, a PWM controller 401 generates a PWM_H1 signal that is provided to the control end of the switch S3, a PWM_L1 signal that is provided to the control end of the switch S4, a PWM_H2 signal that is provided to the control end of the switch S5, and a PWM_L2 signal that is provided to the control end of the switch S6. The PWM controller 301 may generate the control signals PWM_H1, PWM_H2, PWM_L1, and PWM_L2 in accordance with a suitable PWM control scheme, such as by symmetric full bridge control (SFB) or phase shift full bridge (PSFB) control.
[0078] FIG. 21 shows a timing diagram of the power converter 100, in accordance with an embodiment of the present invention. In the example of FIG. 21, the circled numbers on top of the diagram represent repeated phases, and the horizontal axis represents time.
[0079] In the example of FIG. 21, the PWM controller 401 generates the control signals PWM_H1, PWM_H2, PWM_L1, and PWM_L2 in accordance with a symmetric full bridge control scheme. The control signals PWM_H1 and PWM_L1 are symmetric in that they have the same duty cycle and with 180 degree phase shift. Similarly, the control signals PWM_H2 and PWM_L2 are symmetric. Note that the control signals PWM_H1 and PWM_L2 are in-phase, and the control signals PWM_H2 and PWM_L1 are also in-phase.
[0080] The signals shown in FIG. 21 are shown in FIG. 20 (and FIG. 17) and include those of the TR block 120-1. The signals for the other TR blocks 120 are essentially the same as in the TR block 120-1. For convenience of the reader, the current i.sub.LOUT is also labeled as 451, the current i.sub.D1 is also labeled as 452, the current i.sub.MH is also labeled as 453, and the current i.sub.ML is also labeled as 454.
[0081] For symmetric full bridge control as in the example of FIG. 21, the output voltage VOUT of the power converter 100 is given by:
[00006] [0082] where D is the duty cycle of the control signals PWM_H1, PWM_H2, PWM_L1, and PWM_L2, VIN is the input voltage, N is the number of turns of the primary windings L11 and L12, and M is the number of TR blocks 120.
[0083] The operation of the power converter 100 in the case of FIG. 21 is similar to that in the case of FIG. 18, except for some variations that are due to the symmetric full bridge PWM control of the full bridge circuit 110B. The processing of the input voltage VIN by the full bridge circuit 110B, generation of the primary winding current by the full bridge circuit 110B, flowing of the primary winding current from the full bridge circuit 110B to the primary windings to induce secondary winding currents in the secondary windings, and rectifying the secondary winding currents to generate output currents that are provided to the load of the power converter 100 are similar to those in the example of FIG. 18.
[0084] FIG. 22 shows a timing diagram of the power converter 100, in accordance with an embodiment of the present invention. In the example of FIG. 22, the circled numbers on top of the diagram represent repeated phases, and the horizontal axis represents time.
[0085] In the example of FIG. 22, the PWM controller 401 generates the control signals PWM_H1, PWM_H2, PWM_L1, and PWM_L2 in accordance with a phase shift full bridge control scheme. Note that in phase shift full bridge control scheme of FIG. 22, the control signals PWM_H1, PWM_H2, PWM_L1, and PWM_L2 have a fixed duty cycle of about 50%; the control signals PWM_H1 and PWM_L1 are complementary; the control signals PWM_H2 and PWM_L2 are complementary; and the output voltage VOUT is regulated by controlling the phase shift between the control signal PWM_H1 and control signal PWM_H2. The signals shown in FIG. 22 are shown in FIG. 20 (and FIG. 17) and include those of the TR block 120-1. The signals for the other TR blocks 120 are essentially the same as in the TR block 120-1. For convenience of the reader, the current i.sub.LOUT is also labeled as 471, the current i.sub.D1 is also labeled as 472, the current i.sub.MH is also labeled as 473, and the current i.sub.ML is also labeled as 474.
[0086] For phase shift full bridge control as in the example of FIG. 22, the output voltage VOUT of the power converter 100 is given by:
[00007] [0087] where D is the duty cycle of the control signals PWM_H1, PWM_H2, PWM_L1, and PWM_L2, VIN is the input voltage, N is the number of turns of the primary windings L11 and L12, and M is the number of TR blocks 120.
[0088] The operation of the power converter 100 in the case of FIG. 22 is similar to that in the case of FIG. 18, except for some variations that are due to the phase shift full bridge PWM control of the full bridge circuit 110B. The processing of the input voltage VIN by the full bridge circuit 110B, generation of the primary winding current by the full bridge circuit 110B, flowing of the primary winding current from the full bridge circuit 110B to the primary windings to induce secondary winding currents in the secondary windings, and rectifying the secondary winding currents to generate output currents that are provided to the load of the power converter 100 are similar to those in the example of FIG. 18.
[0089] FIG. 23 shows a top view of a TR block 500, in accordance with an embodiment of the present invention. In the example of FIG. 23, the TR block 500 comprises a transformer module 501 and a rectifier module 502 that are disposed horizontally side by side on a surface of a substrate 503. Each of the transformer module 501 and rectifier module 502 is packaged as a single discrete unit. The transformer module 501 and the rectifier module 502 are mounted on a surface of the substrate 503, which may be a printed circuit board (PCB), for example. In one embodiment, the transformer module 501 comprises the previously described transformer T1 or T2, and the rectifier module 502 comprises the previously described rectifier circuit 130. The transformer module 501 and the rectifier module 502 are deployed as a pair to form a TR block 500. A plurality of TR blocks 500 may be mounted on the same substrate 503 or on separate substrates 503.
[0090] FIG. 24 shows a top view of the transformer module 501, in accordance with an embodiment of the present invention. The transformer module 501 includes pads 511-518 for making electrical connections as in FIGS. 1-4. In the example of FIG. 24, the pad 511 is connected to the node 1, which is connected to an end of the series-connected primary windings L11 and L12; the pad 514 is connected to the node 4, which is connected to the other end of the series-connected primary windings L11 and L12; the pads 512 and 513 are intermediate points for electrically connecting the primary winding L12 to the primary winding L11; the pad 515 connects to the first end of the rectifier 121; the pad 516 connects to the first end of the rectifier 122; and the pads 517 and 518 connect to the output voltage VOUT. As can be appreciated, the pad layout of the transformer module 501 may be varied to meet the requirements of the particular application.
[0091] FIG. 25 shows a top view of the TR block 500, in accordance with an embodiment of the present invention. FIG. 25 illustrates an example connection between the transformer module 501 and the rectifier module 502. In the example of FIG. 25, an interconnect 521 connects the pads 517 and 518 to the output voltage VOUT. An interconnect 522 connects the pad 511 to a previous transformer module 501 in a chain of transformer modules 501, and an interconnect 523 connects the pad 514 to a next transformer module 501 in the chain of transformer modules 501. An interconnect 525 connects the pad 515 to the first end of the rectifier 121 in the rectifier module 502, and an interconnect 526 connects the pad 516 to the first end of the rectifier 122 in the rectifier module 502. An interconnect 527 connects the pad 512 to the pad 513. Various electronic components 531-538 may be mounted in the vicinity of the rectifier module 502. These components may include coupling capacitors, resistors, power transistors, integrated circuits, etc.
[0092] FIG. 26 shows a top view of horizontally disposed TR blocks, in accordance with an embodiment of the present invention. In the example of FIG. 26, 6 TR blocks 500 are mounted on a surface of the substrate 503, with each TR block 500 comprising a transformer module 501 and a rectifier module 502. The transformer modules 501 and rectifier modules 502 are disposed in horizontal fashion, side by side on the substrate 503. A bridge circuit (not shown) may be mounted on the substrate 503 or another substrate.
[0093] FIG. 26 also shows other electronic components that are mounted on the substrate 503, such as components 560 (e.g., a gate driver IC), 561 (e.g., a high voltage (e.g., 80V) Field Effect Transistor (FET)), and 562 (e.g., another high voltage FET). Other electronic components on the substrate 503 are not labeled for clarity of illustration.
[0094] FIG. 27 shows a front view of a TR block 600, in accordance with an embodiment of the present invention. The TR block 600 comprises a transformer module 601 and a rectifier module 602. The transformer module 601 and the rectifier module 602 are vertically stacked one on top of another. In the example of FIG. 27, the rectifier module 602 is mounted on a surface of a substrate 603 (e.g., PCB), and the transformer module 601 is mounted on top of the rectifier module 602. Each TR block 600 may have its own substrate 603. A plurality of TR blocks 600 may also share the same substrate 603. In one embodiment, the transformer module 601 comprises the previously described transformer T1 or T2, and the rectifier module 602 comprises the previously described rectifier circuit 130.
[0095] FIG. 28 shows a top view of the rectifier module 602, in accordance with an embodiment of the present invention. In the example of FIG. 28, the rectifier module 602 comprises an integrated circuit (IC) die 610 in which the rectifiers 121 and 122 are fabricated. The IC die 610 may have a copper sink (not shown) on its topmost surface for heat dissipation and for accepting a soldering pad that facilitates attachment of a heat sink. The IC die 610 is mounted on the substrate 603.
[0096] Pads 611-618, which are formed on the substrate 603, are connected by interconnects (not shown) to corresponding nodes and/or pads as per the connections shown in FIGS. 1-4. In the example of FIG. 28, the pads 611 and 612 connect to the output voltage VOUT; the pad 613 is connected to the node 1, which is connected to an end of the series-connected primary windings L11 and L12; the pad 614 is connected to the node 4, which is connected to the other end of the series-connected primary windings L11 and L12; the pad 615 is connected to the node 2; the pad 616 is connected to the node 3; the pad 617 is connected to the first end of the rectifier 121; and the pad 618 is connected to the first end of the rectifier 122.
[0097] FIG. 29 shows a top view of the bottom surface of the transformer module 601, in accordance with an embodiment of the present invention. FIG. 29 shows the bottom surface (as viewed from the top) of the transformer module that will interface with the rectifier module 602 as shown in FIG. 28. More particularly, the pads 711-718 are connected to the pads 611-618, respectively. The transformer module 601 further includes heat sinks 710 that are attached to the IC die 610 for heat dissipation. In one embodiment, the heat sinks 710 are attached to bare copper on a top surface of the IC die 610.
[0098] FIG. 30 shows a top view of the transformer module 601, in accordance with an embodiment of the present invention. FIG. 30 shows the heat sinks 710 as protruding to be visible on the top of the transformer module 601.
[0099] FIGS. 31 and 32 show front views of the TR block 600, in accordance with an embodiment of the present invention. In the example of FIGS. 31 and 32, hashed elements represent metal structures, such as copper interconnects. The interconnects may connect pads of the rectifier module 602 to corresponding pads of the transformer module 601. The IC die 610 may be attached to the heat sinks 710 by way of a metal layer, for example. The transformer T1 or T2 (not shown) may be disposed on the bottom surface or other available space of the transformer module 601.
[0100] FIG. 33 shows a top view of TR blocks 600, in accordance with an embodiment of the present invention. In the example of FIG. 33, 6 TR blocks 600 are mounted on a surface of the substrate 603. FIG. 33 further shows other electronic components that are mounted on the substrate 603, such as components 731 (e.g., a gate driver IC), 732 (e.g., a high voltage (e.g., 80V) FET), and 733 (e.g., another high voltage FET). Other electronic components on the substrate 603 are not labeled for clarity of illustration. A bridge circuit (not shown) may be mounted on the substrate 603 or another substrate.
[0101] While specific embodiments of the present invention have been provided, it is to be understood that these embodiments are for illustration purposes and not limiting. Many additional embodiments will be apparent to persons of ordinary skill in the art reading this disclosure.
