Transconductor circuits with programmable tradeoff between bandwidth and flicker noise are disclosed. An example circuit includes an input port, an output port, a plurality of transistors, and a switch arrangement that includes a plurality of switches, configured to change coupling between the input port, the output port, and the transistors to place the transconductor circuit in a first or a second mode of operation. An input capacitance of the transconductor circuit operating in the first mode is larger than when the transconductor circuit is operating in the second mode. In the first mode, having a larger input capacitance results in a decreased flicker noise because the amount of flicker noise is inversely proportional to the input capacitance. In the second mode, having a smaller input capacitance leads to an increased flicker noise but that is acceptable for wide-bandwidth applications because wide-bandwidth signals may be less sensitive to flicker noise.

Transconductor circuits with programmable tradeoff between bandwidth and flicker noise are disclosed. An example circuit includes an input port, an output port, a plurality of transistors, and a switch arrangement that includes a plurality of switches, configured to change coupling between the input port, the output port, and the transistors to place the transconductor circuit in a first or a second mode of operation. An input capacitance of the transconductor circuit operating in the first mode is larger than when the transconductor circuit is operating in the second mode. In the first mode, having a larger input capacitance results in a decreased flicker noise because the amount of flicker noise is inversely proportional to the input capacitance. In the second mode, having a smaller input capacitance leads to an increased flicker noise but that is acceptable for wide-bandwidth applications because wide-bandwidth signals may be less sensitive to flicker noise.

Some applications require a noise filter to have a very low cutoff frequency. The low cutoff frequency can require the use of a large resistor that is not suitable for integration in an integrated circuit (IC) package. Smaller components can be used to provide a large resistance in a first direction but not in another. In other words, the resistance of these smaller components may be non-reciprocal. A non-reciprocal resistance can affect a response of the noise filter to disruptions at the input or the output. Additionally, these smaller components may not be suitable for low voltage operation. A noise filter is disclosed that provides a high resistance using components that can be included in an integrated circuit package. The noise filter has a reciprocal effective resistance and can utilize technology suitable for low voltage operation.

Some applications require a noise filter to have a very low cutoff frequency. The low cutoff frequency can require the use of a large resistor that is not suitable for integration in an integrated circuit (IC) package. Smaller components can be used to provide a large resistance in a first direction but not in another. In other words, the resistance of these smaller components may be non-reciprocal. A non-reciprocal resistance can affect a response of the noise filter to disruptions at the input or the output. Additionally, these smaller components may not be suitable for low voltage operation. A noise filter is disclosed that provides a high resistance using components that can be included in an integrated circuit package. The noise filter has a reciprocal effective resistance and can utilize technology suitable for low voltage operation.

Certain aspects of the present disclosure provide methods and apparatus for processing signals using a current-mode biquad filter, which may have a tunable bias current and/or tunable capacitance. One example apparatus is a current-mode biquad filter circuit that includes a first input current node, a first capacitive element coupled to the first input current node, a first output current node, a first active filter circuit coupled between the first input current node and the first output current node, and a second active filter circuit coupled between the first input current node and the first output current node. The second active filter circuit is complementary to the first active filter circuit.

A reconfigurable analog filter includes a transimpedance amplifier configured to convert a current signal into a voltage signal, an input capacitor configured to form a current-mode low pass filter together with an input impedance of the transimpedance amplifier, a variable load circuit including at least one switch configured to selectively close a circuit path to provide a resistor and/or a capacitor as a load of the transimpedance amplifier according to a control signal, and a low pass filter configured to filter the voltage signal.

A reconfigurable analog filter includes a transimpedance amplifier configured to convert a current signal into a voltage signal, an input capacitor configured to form a current-mode low pass filter together with an input impedance of the transimpedance amplifier, a variable load circuit including at least one switch configured to selectively close a circuit path to provide a resistor and/or a capacitor as a load of the transimpedance amplifier according to a control signal, and a low pass filter configured to filter the voltage signal.

A calibration operation adjusts a frequency of a ring oscillator to a desired frequency by adjusting programmable RC circuits in the stages of the ring oscillator. The programmable RC circuits have programmable capacitors, resistors, or both. The RC circuits account for most of the delay through the ring oscillator. Another circuit with its own RC time constant is calibrated based on the adjustments made to the RC circuits in the ring oscillator to achieve the desired frequency.

During operation of an analog filter having one or more filter stages is configured to operate in a first configuration. Configuring the analog filter to operate in the first filter configuration includes configuring one or both of i) a filter response of the analog filter and ii) a filter bandwidth of the analog filter. A first set of one or more direct current (DC) offset correction codes corresponding to the first filter configuration are retrieved from a memory. The one or more DC offset correction codes in the first set are converted to one or more first analog DC offset correction signals. While operating the analog filter configured in the first configuration, the one or more first analog DC offset correction signals are applied to the one or more filter stages of the analog filter.

Active feedback is used with two electrodes of a four-electrode capacitive-gap transduced wine-glass disk resonator to enable boosting of an intrinsic resonator Q and to allow independent control of insertion loss across the two other electrodes. Two such Q-boosted resonators configured as parallel micromechanical filters may achieve a tiny 0.001% bandwidth passband centered around 61 MHz with only 2.7 dB of insertion loss, boosting the intrinsic resonator Q from 57,000, to an active Q of 670,000. The split capacitive coupling electrode design removes amplifier feedback from the signal path, allowing independent control of input-output coupling, Q, and frequency. Controllable resonator Q allows creation of narrow channel-select filters with insertion losses lower than otherwise achievable, and allows maximizing the dynamic range of a communication front-end without the need for a variable gain low noise amplifier.