METHOD AND DEVICE FOR OPERATING A RADAR SYSTEM OF A MOTOR VEHICLE

Abstract

A method for operating a radar system of a motor vehicle includes receiving a reception signal, deriving the reception signal from time, ascertaining parameters of an interference signal from the derived reception signal, reconstructing the interference signal from the parameters, and eliminating the interference signal from the reception signal.

Claims

1-10. (canceled)

11. A method for operating a radar system of a motor vehicle, the method comprising: receiving a reception signal; deriving the reception signal from time; ascertaining at least one parameter of an interference signal from the derived reception signal; reconstructing the interference signal from the at least one parameter; and eliminating the interference signal from the reception signal.

12. The method of claim 11, wherein the ascertaining includes ascertaining from extreme values of the derived reception signal a straight line that is a measure for a chronological derivation of a phase response of the interference signal.

13. The method of claim 12, wherein the ascertaining includes ascertaining a slope and an axis intercept of the straight line are ascertained.

14. The method of claim 13, wherein: the radar system includes an IQ mixer; the deriving of the reception signal is performed using a differentiation device; the deriving includes deriving respective portions of the reception signal for each path of the IQ mixer; the straight line is ascertained using an ascertainment device; the respective portions of the reception signal are weighted with the chronological derivation of the phase response; and useful portions of the reception signal are ascertained for each path of the IQ mixer.

15. The method of claim 14, wherein the ascertainment device is provided for only one signal path of the IQ mixer.

16. The method of claim 12, wherein the ascertaining includes ascertaining a zero phase angle of a phase response of the interference signal.

17. The method of claim 11, wherein the ascertaining includes ascertaining from extreme values of the reception signal an amplitude of the interference signal.

18. A device for operating a radar system of a motor vehicle, the device comprising: a differentiation device; an ascertainment device; a reconstruction device; and an elimination device; wherein: the differentiation device is configured to derive a reception signal from time; the ascertainment device is configured to ascertain at least one parameter of the derived reception signal, the at least one parameter representing a measure for a chronological derivation of a phase response of the interference signal; the reconstruction device is configured to reconstruct the interference signal from the at least one parameter; and the elimination device is configured to eliminate the interference signal from the reception signal.

19. The device of claim 18, wherein: the radar system includes an IQ mixer: the ascertainment of the parameters is carried out separately for only one of a plurality of signal paths of the IQ mixer; respective ones of the signal paths are weighted with the respectively ascertained at least one parameter; and an I-component and a Q-component of a useful signal are reconstructed.

20. A non-transitory computer-readable medium on which are stored instructions that are executable by a processor and that, when executed by the processor, cause the processor to perform a method for operating a radar system of a motor vehicle, the method comprising: receiving a reception signal; deriving the reception signal from time; ascertaining at least one parameter of an interference signal from the derived reception signal; reconstructing the interference signal from the at least one parameter; and eliminating the interference signal from the reception signal.

Description

BRIEF DESCRIPTION OF THE DRAWINGS

[0016] FIG. 1 shows a block diagram of a conventional radar system.

[0017] FIG. 2 shows a depiction of a transmission signal of the radar system including a disruptive signal of another radar system.

[0018] FIG. 3 shows a depiction of interference in a reception signal of the radar system.

[0019] FIG. 4a shows a block diagram of a device according to a first example embodiment of the present invention.

[0020] FIG. 4b shows a block diagram of a device according to a second example embodiment of the present invention.

[0021] FIG. 5 shows a basic depiction of a reception signal and of its chronological derivation, according to an example embodiment of the present invention.

[0022] FIG. 6 shows curves of a reception signal over time and of a reconstructed interference signal, according to an example embodiment of the present invention.

[0023] FIG. 7 shows a useful signal purged from an interference signal, according to an example embodiment of the present invention.

[0024] FIG. 8a shows a frequency spectrum before the application of the method.

[0025] FIG. 8b shows a frequency spectrum after the application of the method, according to an example embodiment of the present invention.

DETAILED DESCRIPTION

[0026] FIG. 1 shows a block diagram of a conventional frequency modulated continuous wave radar system (FMCW). In this system, a generator 10 is provided, which feeds a transmission signal to a power splitter 20. Half of the signal is fed from power splitter 20 to a transmission antenna 30 and half is fed to a mixer 60. A reception signal reflected by targets is received by a receiving antenna 40 and is fed to a HF preamplifier 50 and subsequently to a mixer 60. The transmission signal and the reception signal are multiplied by each other with the aid of mixer 60, the result being fed to a filter 70, for example, in the form of a low-pass, to be filtered. From there, the filtered signal passes to a baseband amplifier 80, to an analog-digital converter 90 and subsequently via an interface to a computer (not depicted). With such a FMCW radar system, it is possible in the automotive field, for example, to determine distance, direction and velocity of targets.

[0027] The mutual disruption of linear frequency modulated continuous wave radars (LFMCW radars) is considered in the following.

[0028] FIG. 2 shows multiple ramps f.sub.ego of the transmission signal in a time-frequency diagram, for example, as a signal having a chirp sequence modulation, which interferes in a defined range with a noise signal or interference signal s.sub.int, which is emitted, for example, by a radar system of another motor vehicle. A range delimited by dashes to the left and right of the transmission ramps f.sub.ego represents a reception bandwidth of the radar system, a signal reflected from a target (not depicted) including a signal curve situated in parallel to transmission ramp f.sub.ego within the reception bandwidth, the reflected signal being time delayed relative to transmission ramp f.sub.ego.

[0029] Dashed lines to the right and left of each of transmission ramps f.sub.ego of the transmission signal illustrate an effect of filter 70 of the radar system of FIG. 1, so that an interference effect of the transmission signal with interference signal s.sub.int only occurs in the areas illustrated by circles. The interference in the reception signal of the radar system has a symmetry toward the middle of the interference interval, if the frequency ramps of two RMCW radars intersect. Thus, a precondition of an interference effect is an at least differing slope of the modulation of the transmitting signal and of the interfering signal.

[0030] This can be reflected in increased noise in the frequency spectrum or in a reduced sensibility in the detection of targets. For the cited symmetry, the frequency ramp of the disruptive radar signal must lie completely within the reception bandwidth, which is indicated in FIG. 2 by two dashed lines, which is unlikely if the interference occurs at the beginning or toward the end of the useful signal. Then, the interference is not so strongly disruptive regardless, due to the windowing (for example, Henning window) of the measured data, since the values at the edge of the ramp are only weakly weighted.

[0031] The cause of the symmetry is the phase response φ.sub.int(t) of interference signal s.sub.int over the entire duration of interference T.sub.int, which can be represented mathematically as follows:

[00001]$\begin{array}{cc}{\varphi }_{\mathrm{int}}\left(t\right)-2.Math.\pi .Math.{\int }_{T_{\mathrm{int}}}^{}.Math.f_{\mathrm{int}}\left(t\right).Math.\mathrm{dt}-0& \left(1\right)\end{array}$

[0032] where φ.sub.int(t) is phase response of the interference signal and f.sub.ing is frequency of interference signal s.sub.int, i.e., viewed over the entire interference time period T.sub.int, the phase change adds up to zero. Frequency response f.sub.int(t) of down-mixed interference signal or noise signal f.sub.int results from the difference between interference signal s.sub.int and the transmission signal within the reception bandwidth illustrated with circles in FIG. 2.

[0033] An axial symmetry exists with respect to the position f.sub.int(T.sub.int/2)=0 (point of intersection of interference signal and transmission signal). If the signal is differentiated, a signal symmetrical to its origin forms, the middle of interference duration T.sub.int forming the origin. This is equivalent to an axially symmetrical cosine derived resulting in a negative sine symmetrical to its origin.

[0034] FIG. 3 shows effects of the interference on the time signal of a frequency ramp f.sub.ego of the transmission signal of the host radar. It is apparent that a minimal signal in terms of amplitude occurs on a large part of the time axis. In a range of the time axis between approximately 180 and approximately 270 (qualitative time specifications) on the other hand, an increased amplitude curve is apparent, which is caused by an interference effect of the transmission signal on a transmission signal of another radar system.

[0035] It is now provided to differentiate the received time signal and to obtain information about the specific nature (frequency response) of the down-mixed interference signal from this chronological derivation. This information is utilized in order to thereby deduce the interference portion in the received time signal and to remove it from the time signal or to reduce it. The result is, therefore, a system for repairing the incident time signal or reception signal s.sub.in(t).

[0036] The reception signal s.sub.in(t) of the radar system may generally be represented mathematically as follows:

S.sub.in(t).sup.n=Σs.sub.N+Σs.sub.Int   (2)

[0037] where s.sub.in(t) is the entire reception signal and s.sub.N is the useful signal, and thus forms a superposition of useful signals s.sub.use and interference signals s.sub.int.

[0038] A limitation to a single interference signal s.sub.int is considered below, whereby the approach can also be applied to systems having multiple interference signals. Interference signals s.sub.int can be represented in the time range mathematically as follows:

s.sub.int=A.sub.int−COSφ.sub.int(t)   (3)

where s.sub.int is the interference signal, A.sub.int is amplitude of the interference signal, and φ.sub.int(T) . . . is phase response of the interference signal.

[0039] Phase response φ.sub.int(t) of interference signal s.sub.int results from the difference between the frequency ramps of reception signal s.sub.in and interference signal s.sub.int according to the following mathematical relationship:

[00002]$\begin{array}{cc}{\varphi }_{\mathrm{int}}\left(t\right)=2.Math.\pi .Math.\int f\left(t\right).Math.\mathrm{dt}=2.Math.\pi .Math.\int \left[f_{c,\mathrm{int}}-f_{c,\mathrm{ego}}+\left(\frac{B_{\mathrm{int}}}{T_{c,\mathrm{int}}}-\frac{B}{T_c}\right).Math.t+\frac{B_{\mathrm{int}}}{T_{c,\mathrm{int}}}.Math.\Delta .Math..Math.t\right).Math.\mathrm{dt}& \left(4\right)\end{array}$

[0040] where the parameters are defined as follows:

[0041] T.sub.int chronological duration of the interference signal within the reception bandwidth;

[0042] B frequency swing of the transmitted frequency ramp;

[0043] B.sub.int frequency swing of the frequency ramp of the interference signal;

[0044] T.sub.c chronological duration of the transmitted frequency ramp;

[0045] T.sub.c,int chronological duration of the interference signal;

[0046] f.sub.c,int carrier frequency of the interference signal;

[0047] f.sub.c,ego carrier frequency of the transmission signal;

[0048] Δt chronological shift of interference signal and transmission signal; and

[0049] φ.sub.i zero phase angle of a target response.

[0050] Useful signals s.sub.N can be described as oscillations of constant frequency mathematically as follows:

s.sub.n,i−A.sub.n,i×cos(2πf.sub.beat,I×t+φ.sub.i)   (5)

[0051] where f.sub.beat,I is constant frequency of the nth target response after downmixing.

[0052] FIG. 4a illustrates in a functional manner a first specific embodiment of a device 100 for operating a radar system of a motor vehicle. It is apparent that a Q-portion and an I-portion of reception signal s.sub.in for an IQ mixer are fed to device 100. A chronological derivation of each of the I-portion and of the Q-portion of reception signal s.sub.in is undertaken with the aid of a differentiation device 110.

[0053] If the chronological derivation of reception signal s.sub.in is formed, information can be obtained about the disruptive interference according to the following mathematical relationships:

[00003]$\begin{array}{cc}\frac{d}{\mathrm{dt}}.Math.S_{i.Math..Math.n}\left(t\right)=\frac{d}{\mathrm{dt}}.Math.S_{i.Math..Math.n.Math..Math.t}\left(t\right)+\frac{d}{\mathrm{dt}}.Math..Math.S_{\mathrm{useful},i}\left(t\right)=-A_{\mathrm{int}}.Math.{\varphi }_{\mathrm{int}}\left(t\right).Math.\sin \left({\varphi }_{\mathrm{int}}\left(t\right)\right)+.Math.A_i.Math.\left(2.Math.\pi .Math..Math.f_i\right).Math.\sin \left(2.Math.\pi .Math..Math.f_i.Math.t+{\varphi }_i\right)& \left(6\right)\\ {\varphi }_{\mathrm{int}}\left(t\right)=\frac{d}{\mathrm{dt}}.Math.{\varphi }_{\mathrm{int}}\left(t\right)=2.Math.\pi \left(f_{c,\mathrm{int}}-f_{c,\mathrm{ego}}+\left(\frac{B_{\mathrm{int}}}{T_{c,\mathrm{int}}}-\frac{B}{T_c}\right).Math.t+\frac{B_{\mathrm{int}}}{T_{c,\mathrm{int}}}.Math.\Delta .Math..Math.t\right)& \left(7\right)\end{array}$

[0054] where φ.sub.int(t) is chronological derivation of the phase response of the interference signal and has the form of a straight line, the parameters of which can be determined from derived reception signal s.sub.in. For this purpose, peak values or extreme values above and below a particular threshold value can be listed, since interference signal s.sub.int and its derivation have a higher amplitude than the useful signals. The average value thereof before the derivation supplies amplitude A.sub.int of interference signal s.sub.int. The extreme values in derived input signal s.sub.in can be utilized to determine the parameters of the straight line and thus to determine φ.sub.int(t). In so doing, a straight line is formed by the extreme values for which there are two possible answers, which differ by factor −1 (different slopes). The “false” straight line, i.e., the straight line having the “false” slope results in an increase in the disruption power and can therefore be ignored as implausible. It can be detected, for example, by comparing the extreme values of reconstructed interference signal s.sub.int with the measured extreme values in reception signal s.sub.in.

[0055] The ascertainment in this case takes place with the aid of an ascertainment device 120. The ascertainment of the parameters must be carried out in each case for only one signal component I, Q, the results of the parameter ascertainment being multiplied in a step 130 by the derived signal component with the aid of a multiplier device 130.

[0056] The weighted result is totaled with the Q component with the aid of an elimination device 140 (summing unit), and from this useful signal s.sub.N is obtained. It is then also checked with the aid of a control device 160 whether the interference portion in reception signal s.sub.in is increased or lowered. In the event the interference portion is increased, the false straight line was used, so that the other straight line had to be used to form useful signal s.sub.N. The result, therefore, is a repaired input signal, which has been purged of interference portions. The approach is the same for the Q-path, a subtractor 141 being used as elimination device 141.

[0057] As depicted in FIG. 5, the chronological derivation of useful signals s.sub.N is very small in undisrupted areas I of reception signal s.sub.in as compared to the derivation of a reception signal s.sub.in in area II subject to interference. Thus, interference occurs exclusively in area II. The differentiated cosine signal is then weighted in such a way that the interference portion exhibits the same amplitude curve as in the sinus signal. The weighting must therefore be (φ.sub.int(t)).sup.−1, which has a curve similar to f(x)=x.sup.−1. Since (φ.sub.int(t)).sup.−1 tends toward the infinite for the middle of the interference duration, an upper limit for this should be set in the system. Finally, the weighted signal is subtracted from the sinus signal.

[0058] The derivation of the I-component of reception signal s.sub.in can be represented mathematically as following:

[00004]$\begin{array}{cc}\frac{d}{\mathrm{dt}}.Math..Math.S_{\mathrm{useful}}+\frac{d}{\mathrm{dt}}.Math.S_{i.Math..Math.n.Math..Math.t}\approx -A_{\mathrm{int}}.Math.{\varphi }_{\mathrm{int}}\left(t\right).Math.\sin \left({\varphi }_{\mathrm{int}}\left(t\right)\right)& \left(8\right)\end{array}$

[0059] Applicable for the Q-component of reception signal s.sub.in is:

ΣA.sub.i.Math.sin(f,t+φ.sub.i)+A.sub.int.Math.sin(φ.sub.int(t))   (9)

[0060] Sum and weighting with (φ.sub.int(t)).sup.−1 result in:

ΣA.sub.i.Math.sin(f,t+φ.sub.i)+A.sub.int.Math.sin(φ.sub.int(t))−(φ.sub.int(t)).sup.−1.Math.A.sub.intφ.sub.int(t).Math.sin(φ.sub.int(t))=s.sub.N   (10)

[0061] In this way, reception signal s.sub.in was purged of the interference portion or interference signal s.sub.int, so that a disruption-free useful signal s.sub.N is provided. To a certain degree, there is also a loss of useful signal s.sub.N, since the weighted I-component still contains parts of useful signal s.sub.N.

[0062] A high degree of accuracy of the parameter estimation is advantageously not absolutely necessary in the case of device 100 of FIG. 4a in order to superpose the terms in such a way that the amplitudes in the interference portions are cancelled out. Moreover, with this variant it is advantageously not necessary to determine a zero phase angle of the phase response.

[0063] A second specific embodiment of device 100 is schematically depicted in FIG. 4b. In this case, no IQ mixer is used in the radar system, interference signal s.sub.int being reproduced from the amplitude and the frequency of reception signal s.sub.in and being subtracted from reception signal s.sub.in. Differentiation device 110 is the same as in the specific embodiment of device 100 of FIG. 4a, as is ascertainment device 120. In addition to the slope and to the axis intercept of the straight line, the zero phase angle of the phase response must also be determined in this case, for example, by ascertaining the phase relation of reception signal s.sub.in in the middle of interference duration T.sub.int (approximately in the middle of area II of FIG. 5). A chronological duration of the interference is determined either via the outermost collected peak values during the threshold value detection or via the highest occurring frequency due to the limited reception bandwidth. Since the frequency response of filter 70 has an influence on reception signal s.sub.in, previous knowledge of this can be utilized to improve an accuracy of device 100.

[0064] On the basis of measured data depicted in the figures, it can be recognized that intersecting interference ramps in the time range in fact appear as in the simulation of FIG. 3. Previous publications show interferences, in which only a few (approximately 3 to 5) signal values are influenced by the interference. The difference in the method according to the present invention is attributed to the high receiver bandwidth and sampling rate associated with the extreme steepness of the frequency ramps, which are used, in particular, in a chirp sequence modulation. Thus, it can be assumed that the method according to the present invention is particularly well-suited for the chirp sequence modulation.

[0065] For measuring cycles with occurring interference, the attempt was made to reconstruct the interference signal by the estimation with the aid of device 100 in FIG. 4b.

[0066] In FIG. 6, reception signal s.sub.in is represented by a solid line and the interference signal reconstructed from derived reception signal s.sub.in is represented by a dashed line.

[0067] In FIG. 7, the measured reception signal s.sub.in and the difference between reception signal s.sub.in and reconstructed interference signals s.sub.int is represented as useful signal s.sub.N. The estimation of the parameters should preferably be very precise in order to carry out a meaningful reconstruction.

[0068] FIG. 8a shows a frequency spectrum of a radar system before the repair with the aid of the method according to the present invention. A higher noise portion in the spectrum is apparent, no close targets being present.

[0069] FIG. 8b shows the frequency spectrum after the repair. In the center of the spectrum, it is apparent that the noise has dropped by approximately 10 dB, and individual targets are also recognizable as lines. This is to indicate that the noise portion in the reception signal can be reduced by removing the interference portion.

[0070] Device 100 can be advantageously implemented as a software program in the radar system. It is also conceivable, however, to implement device 100 as a software program in one or multiple control units of a motor vehicle.

[0071] In summary, example embodiments of the present invention provide a method and a device with which a disruptive interference portion can be eliminated from a reception signal of a radar system. In this way, a detection accuracy can be increased and a signal-to-noise ratio of received signals can be improved.

[0072] Although the present invention was described above with reference to specific exemplary embodiments, it is not limited thereto. Those skilled in the art may therefore also implement specific embodiments not described above without departing from the essence of the present invention.